Monolithically integrable squarewave pulse generator

Abstract

Monolithically integrable squarewave pulse generator having a capacitor acted upon by two bucking constant-current sources, the capacitor having one terminal connected to the two constant-current sources as well as to a non-inverting input of an operational amplifier connected as a Schmitt trigger, and the capacitor having another terminal tied to reference potential, one of the constant-current sources being operative for charging the capacitor, including a third current source connected to the one capacitor terminal connected to the two constant-current sources for aiding the one constant-current source in charging the capacitor, the third current source being responsive to an adjustable potential of the one capacitor terminal; and the Schmitt trigger having an output connected through a decoupling element to signal output of the squarewave pulse generator.

Description

The invention relates to a monolithically integrable squarewave pulse generator with a capacitor which is acted upon by two bucking constant-current sources, one terminal of the capacitor being connected to the two constant-current source and, in addition, to the non-inverting input of an operational amplifier connected as a Schmitt trigger, and the other terminal of the capacitor being tied to reference potential (ground).

A similar squarewave pulse generator is described in the book "Halbleiter-Schaltungstechnik" (Semiconductor Circuit Engineering) by Tietze-Schenk (1978 edition) on page 443. In accordance with experience, this heretofore known squarewave pulse generator is disadvantageous in that the squarewave pulses provided thereby deviate from the expected result all the more disturbingly, the higher the operating frequency of the generator, which is observed with respect to the frequency and duty cycle, especially if the duty cycle can be selected freely. As will be shown hereinafter, in connection with FIG. 1 of the drawing herein, the cause of these undesirable deviations is primarily the delay between the ascertainment of a threshold critical for the system and the reaction of the system.

To meet this problem, the detrimental signal delay times can be shortened with additional circuitry cost, for example, by using a so-called unsaturated circuit technique in the construction of the generator, as well as by the higher current drain caused thereby. It would therefore be desirable to reduce both disadvantages and to avoid nevertheless, the disadvantage of the heretofore known squarewave generators of the type defined hereinbefore. It is accordingly an object of the invention to solve this problem.

To this end, the squarewave pulse generator defined at the introduction hereto is constructed, in accordance with the invention, in a manner that the terminal of the capacitor acted upon by the two constant-current sources is connected to a further current source which aids the constant-current source, causing the capacitor to be charged, and which responds with an auxiliary voltage U_H1 to an adjustable potential of this capacitor terminal, and that furthermore, the output of the Schmitt trigger is connected to the signal output of the generator through a decoupling element.

The effect of such a device is that the discharge of the capacitor below the desired threshold of the capacitor voltage is largely prevented.

It is then advantageous if, additionally, the pulse width of the squarewave voltage is corrected i.e. cut, for small duty cycles.

To this end, in accordance with a further feature of the invention, the capacitor terminal acted upon by the two constant-current sources is connected by a three-pole semiconductor switch to the input of a first inverter and the output of the latter is connected through a second inverter to the signal output of the generator.

Regarding the dimensioning of the three current sources, the following can be stated: If the current I₁ supplied by the first constant-current source serves for charging the capacitor, and the current I₂ supplied by the second constant-current source for discharging the capacitor, and if I₃ is the current supplied by the third current source, which is adjustable, the three current sources must be matched to one another so that

I₃ >I₂ >I₁. (1)

Other features which are considered as characteristic for the invention are set forth in the appended claims.

Although the invention is illustrated and described herein as embodied in a monolithically integrable squarewave pulse generator, it is nevertheless not intended to be limited to the details shown, since various modifications and structural changes may be made therein without departing from the spirit of the invention and within the scope and range of equivalents of the claims.

The construction and method of operation of the invention, however, together with additional objects and advantages thereof will be best understood from the following description of specific embodiments when read in connection with the accompanying drawings, in which:

FIG. 1 is a plot diagram showing, at low frequencies, the behavior of the heretofore known squarewave pulse generators;

FIG. 2 is a diagram similar to that of FIG. 1 at higher frequencies;

FIG. 3 is a circuit diagram of one embodiment of the monolithically integrable squarewave pulse generator according to the invention;

FIGS. 4 and 5 are diagrams similar to that of FIG. 2 showing the behavior of the embodiment of FIG. 3 at high frequencies;

FIG. 6 is a circuit diagram like that of FIG. 3 of the embodiment of the invention supplemented in a manner similar to a shortfall so as to prevent the upper threshold of the capacitor voltage from being exceeded; and

FIG. 7 is a circuit diagram of another embodiment of the invention.

FIGS. 8 and 9 are circuit diagrams of embodiments of the current sources S1 and S2 of FIG. 3, respectively.

Referring now to the drawing, and first, particularly to FIG. 1 thereof, there is shown a sawtooth voltage U_C at a capacitor C and a squarewave voltage U_A derived therefrom, as are obtained at low frequencies by means of a squarewave pulse generator of the type described and defined at the introduction hereto. Voltages U₁ and U₂ indicate the upper and the lower threshold of U_C. Delay time τ is the delay between the recognition of a threshold and the reaction of the voltage U_A. The ratio t₂ /t₁ determines the duty cycle. The pulse width of U_A corresponds to the discharge time of the capacitor C between U₁ and U₂. It then follows:

Frequency F=(t₁ +t₂)-1 =f(U₁, U₂, C)

Pulse width t₂ =t_ab.

The picture changes, as seen in FIG. 2, upon a transition to the operation of the conventional system at higher frequencies. Then we have:

Frequency F=(t₁ +t₂)-1 =f(U'₁, U'₂, U₁, U₂, C)<f(U₁, U₂, C)

and for the pulse width t₂

t₂ =f(τ, t_ab, U'₁)≈t_ab +τ₁

(U'₁ -U₁)<<(U₂ -U'₂) (for low duty cycle),

the significance or meaning of the individual times and voltages being indicated in the figure because of the delay τ, the discharge phase sets in too late. Therefore the capacitor voltage U_c, rises beyond U₁ to U'₁. Correspondingly, the discharge phase is terminated too late i.e. U_C falls below U₂ to U'₂.

A preferred embodiment of a device according to the invention is shown in FIG. 3, to which reference is now made. That portion of the device in FIG. 3 which corresponds to the conventional construction is shown framed by broken lines, with the exception of the decoupling element K₂.

One terminal of the capacitor C, which determines or establishes the characteristic of the squarewave pulse generator, is connected to reference potential, i.e. ground; whereas the other terminal thereof is the point of attack of two constant-current sources S₁ and S₂, which are of conventional construction, the current source S₁ supplying the charging current I₁ and the current source S₂ the discharging current I₂. The terminal of the capacitor C acted upon by the two current sources S₁ and S₂ is further connected to the non-inverting input of an operational amplifier K₁ and, in addition, to the emitter of a bipolar transistor T₂ which represents the three-pole switch and is controlled by an auxiliary voltage U_H1.

The inverting input of the operational amplifier K₁ is connected via a voltage divider formed by the two resistors R₁ and R₂ to an operating potential U and is furthermore connected via the resistor R₃ to the collector of another bipolar translator T₁, the emitter of which is connected to reference potential (ground) and the base of which is tied to the output of the operational amplifier K₁, so that the operational amplifier K₁ is suitably supplemented to form a Schmitt trigger. Another feature of this arrangement is that the output of the Schmitt trigger can be fed back to the non-inverting input of the operational amplifier K₁ via a switch, particularly one realized by a transistor, and via the current source S₂.

In the case of the embodiment of the invention shown in FIG. 3, the current source S₁ is realized by a pnp-transistor, the emitter of which (predominantly via a series resistor) is at reference potential and the collector of which is connected to the capacitor C and to the non-inverting input of the operational amplifier K₁, while the base is acted upon by an adjustable d-c potential. The same applies to the constant-current source S₂, except that, in the case of the embodiment of FIG. 3, an npn-transistor is provided therefor. FIG. 8 shows that the current source S1 may be in the form of two pnp transistors 1 and 2 which are connected together at their bases. The emitter of each transistor is connected to the operating potential U while the bases of the transistors and the collector of transistor 2 are connected through a resistor R to reference potential. FIG. 9 shows that the current source S2 may be in the form of two npn transistors 3 and 4 which are connected together at their bases as well. The emitter of each transistor is connected to reference potential while the collector of transistor 3 is connected through a resistor R to the operating potential U. The transistor 5 in FIG. 9 represents the switch which is diagrammatically shown in FIG. 3 to be connected to the current source S2. The switch which is given reference symbol S in FIG. 9 is an npn transistor with an emitter connected to reference potential, a collector connected to the bases of transistors 3 and 4 as well as to the collector of transistor 3, and a base which is at zero volts when the switch S is in the closed position. Such current sources are conveniently used in the art and the transistors 2 and 3 could also be omitted so that the bases of transistors 1 and 4 would be connected to a potential for determining the currents I₁ and I₂, such as from a voltage divider. The transistor T₁, which supplements the operational amplifier K₁ to form the Schmitt trigger, is an npn-transistor in the case of the embodiment of FIG. 3.

It is thus in keeping with the invention that the output of the Schmitt trigger is connected via a decoupling element to the signal output SA of the squarewave pulse generator. The decoupling element which, in its simplest form may be a transistor and, indeed, an npn-transistor in the case of the embodiment of FIG. 3, is provided in the system shown in FIG. 3 by a non-inverting amplifier K₂.

It is further in keeping with the invention that an additional current source is connected via the three-pole switch T₂ to the capacitor C in the hereinaforementioned sense. In the case of the embodiment of FIG. 3, the switching transistor T₂ is realized by an npn-transistor, the base of which is connected via a series resistor R₄ to an auxiliary voltage U_H1 and the collector of which is connected, via a voltage divider realized by the two resistors R₅ and R₆ and, indeed, through the series connection of the two resistors of the voltage divider, to the operating potential U.

By means of a bipolar transistor T₃ (in the case of the embodiment of FIG. 3, a pnp-transistor), the voltage divider is supplemented to form a first inverter, in that the base of the transistor T₃ is connected to the tap between R₅ and R₆ and the emitter is connected to the end point of the voltage divider at which the operating potential U, is applied. The output of the first inverter is realized by the collector of the transistor T₃.

The latter is connected via a resistor R₇ to the base of an additional bipolar transistor T₄ (in the case of the embodiment of FIG. 3, an npn-transistor) which represents the second inverter, the emitter of the transistor T₄ being connected to reference potential and the collector to the signal output SA and thus to the output of the decoupling element K₂.

With respect to the operation of the novel system, the following can be said: The current I₁ charges the capacity C up to the voltage U₁ and thereby provides the rising flank of a sawtooth voltage and consequently defines the pulse interval t₁. The current I₂ serves to discharge the capacitor C to the voltage U₂ and thus provides the falling flank of the sawtooth voltage, and thereby defines the pulse width t₂. ##EQU1## is effected by the operational amplifier K₁ acting as a comparator and the transistor T₁ with the delay τ. Thereafter, the discharge of the capacitor C is initiated by switching-on the discharge current I₂.

The squarewave voltage U_A is taken off via the decoupler K₂. The improvement of the function generator according to the invention is achieved primarily by the transistor T₂, T₃ and T₄ as well as by the resistors R₅, R₆ and R₇ in conjunction with the supply potential U and the auxiliary voltage U_H1.

The optimum value of the auxiliary voltage U_H1 for U₂ =2V, for example, follows: ##EQU2## Then, as can be seen from FIG. 5 which is an enlarged fragmentary view of FIG. 4, the tangent to the linear portion of the shape of U_C, at the right-hand side of FIG. 5, intersects the falling flank of U_C in a further frequency range in the vicinity of the threshold U₂ (intersection 3). The frequency is therefore influenced only little by the discharge of the capacitor C below the threshold U₂ to the voltage U₀.

As soon as the voltage U_C has fallen below the switching threshold U₂ to the value of the auxiliary voltage U_H1 minus the base emitter threshold voltage of the switching transistor T₂, charging of the capacitor C by the current I₃ is effected, in addition to the regular discharge of the capacitor C by the current I₂, for which purpose I₃ >I₂, previously mentioned herein. This limits the discharge of the capacitor to the voltage U₀ (see FIG. 4 in comparison with FIGS. 1 and 2). The current I₃, which is set by the resistors R₅ and R₆, switches the transistor T₃ and, thereby, also the transistor T₄ via the resistor R₇ into condition after the delay time. Thus, the voltage jump of U_A from the high to the low level is affected in a given time prior to switching through the decoupler K₂ to low output voltage.

There is virtually no increase in current drain of the generator due to the supplementation or improvement proposed by the invention in comparison to the conventional construction, because the circuit components which have been added to the previously known system become operative only at higher frequencies and the currents I₃ and I₄ are then only current pulses of brief duration.

The prevention of a discharge of the capacitor down to a range considerably below the desired threshold, which is ensured by a system according to the invention, and additional reduction of the pulse width for small duty cycles therefore increase the upper frequency limit in function generators without considerable expense of circuit means in comparison with that for heretofore known squarewave pulse generators. Thus, for example, it has been possible to raise a lower frequency limit below 25 kHz of a system constructed without the additional features proposed by the invention, to a frequency limit above 100 kHz by introducing the supplemental features mentioned hereinbefore.

The embodiment of a squarewave pulse generator corresponding to that of the invention shown in FIG. 3 is distinguished by its simplicity. One can arrive at more complicated possibilities, for example, through a different construction of the two inverters or the decoupler, but such variations, however, have at most small advantages over the embodiment described and illustrated hereinbefore, so that a discussion of such possibilities is believed to be unnecessary.

In addition to the three current source in the embodiment of FIG. 3, a fourth current source is required in the embodiment of FIG. 6, and represents a threshold switch controlled by an auxiliary voltage U_H2 and aiding the discharging current I₂. The current I₄ supplied by this fourth current source is adjusted so that it meets the requirements

I₄ >I₁ (3).

The possibility of a further improvement of the invention mentioned hereinbefore, and realizable, as shown in FIG. 6, by connecting a fourth current source to the capacitor C, in principle, corresponds to a great extent to the previously described embodiment of the invention. In detail, what may be said about this additional improvement is that, after the capacitor voltage has surpassed the upper threshold U₁, the threshold switch formed of the transistor T₅, which is controlled by the auxiliary voltage U_H2, switches on the current I₄ and thereby prevents further charging of the capacitor C.

The circuit of this improved second embodiment of the invention shown in FIG. 6 corresponds to that of FIG. 3, with the addition of a pnp-transistor T₅, the emitter of which is connected to the terminal of the capacitor C, which is acted upon by the constant-current sources and is connected to the emitter of the npn-transistor T₂ as well as to the non-inverting input of the operational amplifier K₁, while the collector of the transistor T₅ is at reference potential (ground) and the base thereof at the auxiliary voltage U_H2.

In the embodiments of the invention heretofore described, the duty cycle i.e. the ratio t₂ /t₁, is smaller than 1. If the duty cycle is greater than 1, it is advantageous to use a further modification of the circuits shown in FIGS. 3 and 6, respectively, namely that of FIG. 7. In this embodiment of FIG. 7, the Schmitt trigger made up of the operational amplifier K₁ and the transistor T₁ corresponds to the construction thereof in FIG. 3. The same is true for the connection of the capacitor C. Since, contrary to the embodiment according to FIG. 3, the charging current and not the discharging current is switched in the embodiment of FIG. 7, the role of the constant-current sources supplying the currents I₁ and I₂ is interchanged. This means that the current I₂ to be switched serves in the embodiment of FIG. 7 as the charging current and the current, which is not to be switched, as the discharging current. With respect to the circuit of FIG. 7, it is also noted that the bipolar transistor T₂ which is to be controlled at the base thereof by the auxiliary voltage U_H1, is of the pnp type, and the emitter of the transistor T₂ is connected to the stated terminal of the capacitor C, while the collector, via a resistor R₈, is connected to reference potential (ground), the auxiliary voltage U_H1 being applied to the base of the transistor T₂ via a series resistor R₄.

The circuit output is further realized by an OR gate K'₂ in FIG. 7, the one input of which is addressed by the output of the Schmitt trigger and the second input by the collector of the switching transistor T₂. The transistor T₂ supplies the current I₃.

An npn-transistor T₅, which can be controlled at the base thereof by the auxiliary voltage U_H2, is connected by the collector thereof to the operating potential U and by the emitter thereof to the terminal of the capacitor which, in turn, is also connected to the non-inverting input of the operational amplifier K₁ and to the emitter of the transistor T₂. This transistor T₅ carries the current I₄.

The circuit must be laid out so that the condition I₃ >I₂ >I₁ and I₄ >I₁ are met.

The reason for replacing the amplifier K₂ of FIGS. 3 and 6 with an OR gate K₂ ' in FIG. 7 is that in the arrangement according to FIG. 3, for example, the signal output voltage U_A must be brought from the level HIGH to the level LOW, while in the arrangement according to FIG. 7, exactly the reverse is proposed.

Claims

1. In a monolithically integrable squarewave pulse generator having a capacitor acted upon by two bucking constant-current sources, the capacitor having one terminal connected to the two constant-current sources as well as to a non-inverting input of an operational amplifier connected as a Scmitt trigger, and the capacitor having another terminal tied to reference potential, one of the constant-current sources being operative for charging the capacitor, the improvement comprising a third current source in the form of a transistor being normally off and having an electrode connected to the one capacitor terminal connected to the two constant-current sources and a base and an auxiliary voltage source connected to the base of the said third current source transistor for firing said third current source transistor during the discharge period of the capacitor because of the difference in potential between the base thereof and the capacitor, the Schmitt trigger having an output connected to signal output of the squarewave pulse generator.

2. pulse generator according to claim 1 wherein the constant-current sources are matched to one another so that a current I₁ supplied by the one constant-current source for charging the capacitor has the following relationship to a current I₂ supplied by the second constant-current source for discharging the capacitor and to an adjustable current I₃ supplied by said third current source:

I₃ >I₂ >I₁.

3. pulse generator according to claim 1 including two serially connected inverters acted upon by a common operating potential and reference potential, the one capacitor terminal connected to the two constant-current sources being tied through said third current source transistor to an input of one of said inverters, said one inverter having an output tied through the other of said inverters to signal output of the pulse generator.

4. pulse generator according to claim 3 wherein said third current source transistor is a bipolar transistor and the electrode thereof is an emitter being also connected to the non-inverting output of said operational amplifier and including another electrode thereof being a collector connected to both of said inverters.

5. pulse generator according to claim 4 wherein said auxiliary voltage is applied over a series resistance connected to said base of said bipolar transistor.

6. pulse generator according to claim 4 wherein one electrode of said bipolar transistor is tied through a resistor to a circuit node, said circuit node being tied to operating potential through another resistor and to the emitter-base path of one of said inverters in the form of another bipolar transistor connected in parallel with said other resistor, said other bipolar transistor having a collector connected via a third resistor to the base of the other of said inverters in the form of another transistor, said other transistor having an emitter tied to operating potential and a collector connected to signal output of the pulse generator.

7. pulse generator according to claim 6 wherein a bipolar transistor supplementing said operational amplifier to said Schmitt-trigger and located between the inverting input and output of said operational amplifier, as well as said bipolar transistor forming said third current source transistor and said other of said inverters which is also formed as a transistor are all of the npn-type; and said one of said inverters being in the form of a transistor of the pnp-type.

8. pulse generator according to claim 7 including yet another bipolar transistor complementary to said bipolar transistor forming said third current source transistor having mutually connected emitters, said complementary transistor having a base to which an auxiliary voltage is applied and a collector to which reference potential is applied.

9. pulse generator according to claim 2 including a first bipolar transistor serving as said third current source transistor having a base to which an auxiliary voltage is applied, a collector at reference potential, and an emitter connected both to the one terminal of the capacitor connected to the two constant-current sources to which the charging current I₁ and discharging current I₂ are applied as well as to an emitter of a second bipolar transistor, complementary to said first bipolar transistor, said second bipolar transistor having a collector tied to reference potential and a base to a further auxiliary voltage, an OR-gate forming the signal output of the pulse generator and having two inputs, said collector of said first bipolar transistor forming said third current source transistor connected to one of said inputs of said OR-gate, and said output of said Schmitt trigger to the other of said inputs of said OR-gate, and all of the components of the pulse generator being of such dimension that both ,f the currents I₁ and I₂ delivered by said constant-current sources to the capacitor, as well as a third current I₃ fed through said first bipolar transistor serving as said third current source transistor as well as a fourth current I₄ passing through a third bipolar transistor complementary to said first bipolar transistor serving as said third current source transistor have the mutual relationship

I₃ >I₂ >I₁ and I₄ >I₁.

10. pulse generator according to claim 1, including a decoupling element connected between the output of Schmitt trigger and signal output of the squarewave pulse generator.