The invention an optical system and a method for automatically controlling the gain of a receiver in an optical system. The optical system includes an optical receiver, a pulse capture unit, and an automatic gain control. The pulse capture unit includes a capture unit capable of capturing an optical signal received by the optical receiver; and, a process unit capable of processing the captured optical signal. The automatic gain control is capable of controlling the gain of the optical receiver responsive to the content of the processed optical signal. The method includes comparing the intensity of at least one returned pulse, and typically a plurality of returned pulses, to a predetermined value; and controlling the gain of an optical detector responsive to the comparison. In addition, the maximum gain is controlled by a noise limit in some implementations.
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17. A method for automatically controlling the gain of a receiver in an optical system, comprising
comparing the intensity of a returned pulse to a target value, including comparing the intensity to a median value of a plurality of returned pulses; and
controlling the gain of an optical detector responsive to the comparison.
24. A method for automatically controlling the gain of a receiver in an optical system, comprising:
comparing the intensity of a returned pulse to a target value;
controlling the gain of an optical detector responsive to the comparison;
clamping the upper bound of the controlled gain, including:
detecting a noise event; and
decreasing the gain; and
gating the detection.
33. A method comprising:
receiving a plurality of return pulses;
generating an optical signal including the received return pulses;
capturing the return pulses in the optical signal;
processing the captured return pulses;
detecting a noise event in the capture of the return pulses; and
automatically controlling the gain in generating the optical signal responsive to the intensity of the processed return pulses and responsive to the detected noise event, including comparing the intensity of the returned pulses to a target value, wherein comparing the intensity of the returned pulses to the target value includes comparing the intensity to a median value of a plurality of returned pulses.
9. An apparatus, comprising:
an optical detector;
a threshold unit capable of converting an analog optical signal received by the optical detector to a digital representation thereof;
a capture unit capable of capturing the digital representation of the received optical signal;
a process unit capable of processing the captured digital representation; and
an automatic gain control capable of controlling the gain of the optical detector responsive to the content of the processed digital representation, wherein:
the automatic gain control drives the gain higher responsive to determining that the intensity of a return pulse in the optical signal is lower than a target value and drives the gain lower responsive to determining that the intensity of the return pulse in the optical signal is higher than the target value; and
the target value is the median intensity value of the processed return pulses.
1. An apparatus, comprising:
an optical detector;
a threshold unit capable of converting an analog optical signal received by the optical detector to a digital representation thereof;
a capture unit capable of capturing the digital representation of the received optical signal;
a process unit capable of processing the captured digital representation; and
an automatic gain control capable of controlling the gain of the optical detector responsive to the content of the processed digital representation, wherein the automatic gain control drives the gain higher responsive to determining that the intensity of a return pulse in the optical signal is lower than a target value and drives the gain lower responsive to determining that the intensity of the return pulse in the optical signal is higher than the target value, the automatic gain control including:
an intensity median computation circuit capable of comparing the intensity of the return pulse to a predetermined value and outputting a first signal indicating the result of the comparison;
an up/down counter capable of receiving the first signal, incrementing and decrementing responsive to the first signal, and outputting a second signal proportional to the count therein;
a digital to analog converter capable of converting the second signal to an analog signal; and
an attenuator receiving the analog signal and attenuating a gain signal responsive to the analog signal.
4. The apparatus of
5. The apparatus of
a time demultiplexer capable of demultiplexing the digitized representation; and
a line encoder capable of encoding the demultiplexed digitized representation.
6. The apparatus of
7. The apparatus of
a convolution circuit capable of generating a filtered signal; and
a peak detect circuit capable of detecting the peak amplitude of the filtered signal.
8. The apparatus of
12. The apparatus of
13. The apparatus of
a time demultiplexer capable of demultiplexing the digitized representation; and
a line encoder capable of encoding the demultiplexed digitized representation.
14. The apparatus of
15. The apparatus of
a convolution circuit capable of generating a filtered signal; and
a peak detect circuit capable of detecting the peak amplitude of the filtered signal.
16. The apparatus of
18. The method of
incrementing and decrementing an up/down counter;
converting an output of the counter proportional to the content thereof to an analog signal; and
attenuating a power supply signal proportionally to the amplitude of the analog signal.
19. The method of
20. The method of
22. The method of
detecting a noise event; and
decreasing the gain.
23. The method of
decrementing an up/down counter;
converting an output of the counter proportional to the content thereof to an analog signal; and
attenuating a power supply signal proportionally to the amplitude of the analog signal.
25. The method of
enabling the detection in a time period in which a false returned pulse is expected; and
disabling the detection otherwise.
26. The method of
27. The method of
incrementing and decrementing an up/down counter;
converting an output of the counter proportional to the content thereof to an analog signal; and
attenuating a power supply signal proportionally to the amplitude of the analog signal.
28. The method of
29. The method of
enabling the comparison in a time period in which a true return pulse is expected; and
disabling the comparison otherwise.
31. The method of
detecting a noise event; and
decreasing the gain.
32. The method of
decrementing an up/down counter;
converting an output of the counter proportional to the content thereof to an analog signal; and
attenuating a power supply signal proportionally to the amplitude of the analog signal.
34. The method of
comparing the intensity of each true return pulse to a target value; and
adjusting the gain of an optical detector responsive to the comparison.
35. The method of
incrementing and decrementing an up/down counter responsive to the comparison;
converting an output of the counter proportional to the content thereof to an analog signal; and
attenuating a power supply signal proportionally to the amplitude of the analog signal.
36. The method of
38. The method of
generating a train of optical pulses;
scanning a field of view while transmitting the train of optical pulses such that, upon encountering an object in the field of view, they are reflected as the return pulses.
39. The method of
40. The method of
41. The method of
detecting the received return pulses; and
digitizing the detected return pulses.
42. The method of
sampling the optical signal; and
encoding the samples of the optical signal.
43. The method of
44. The method of
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1. Field of the Invention
The present invention pertains to laser detection and ranging (“LADAR”) systems, and, more particularly, to the pulse capture electronics of LADAR systems.
2. Description of the Related Art
A need of great importance in some military and civilian operations is the ability to quickly detect, locate, and/or identify objects, frequently referred to as “targets,” in a “field of view.” A common problem in military operations, for example, is to detect and identify targets, such as tanks, vehicles, guns, and similar items, which have been camouflaged or which are operating at night or in foggy weather. It is important in many instances to reliably distinguish between enemy and friendly forces. As the pace of battlefield operations increases, so does the need for quick and accurate identification of potential targets as friend or foe, and as a target or not.
Useful techniques for identifying targets have existed for many years. For instance, in World War II, the British developed and utilized radio detection and ranging (“RADAR”) systems for identifying the incoming planes of the German Luftwaffe. RADAR uses radio waves to locate objects at great distances even in bad weather or in total darkness. Sound navigation and ranging (“SONAR”) has found similar utility and application in environments where signals propagate through water, as opposed to the atmosphere. While RADAR and SONAR have proven quite effective in many applications, they are inherently limited by a number of factors. For instance, RADAR is limited because it uses radio frequency signals and large antennas used to transmit and receive such signals. Thus, alternative technologies have been developed and deployed.
One such alternative technology is laser detection and ranging (“LADAR”). Similar to RADAR systems, which transmit radio waves and receive radio waves reflected from objects, LADAR systems transmit laser beams and receive reflections from targets. In LADAR systems, brief laser pulses are generated and transmitted via an optical scanning mechanism. Some of the transmitted pulses strike a target and are reflected back to a receiver associated with the transmitter. The time between the transmission of a laser pulse and the receipt of the reflected laser pulse (a “return pulse”) is used to calculate the “range” from the target to the object that receives the return pulse.
Because LADAR provides range information, the data is “three-dimensional,” i.e., it provides information about the target in three dimensions. Typically, these dimensions are range, azimuth, and elevation. The shorter wavelengths of light signals (relative to radio signals) also provide much higher resolution and tighter beam control. These attributes of LADAR data greatly assist not only with target location, but also target identification. Thus, in many respects, LADAR systems can provide much greater performance than can, e.g., RADAR and SONAR systems.
The evolution of one particular LADAR system can be traced by reviewing the following issued U.S. Letters Patent:
One concern with virtually all LADAR receivers is the “gain” of their detectors. The gain controls the amount of amplification applied by the detector to a return pulse when it is received. The gain should be commensurate with the intensity of the return pulse. If the intensity of the return pulse is high, then the gain of the detector should be low to avoid over-saturating the detector's components. On the other hand, if the intensity is low, the gain should be high to facilitate subsequent processing, although not so high that “noise” is reported as a return pulse.
Setting the detector's gain, however, is fraught with many difficulties. The intensity of return pulses can vary wildly from one moment to the next and creates difficulty in setting the gain for any particular intensity level. Setting the gain arbitrarily high unnecessarily risks over-saturating the detector's components for high intensity returns and erroneously reporting noise as returned pulses. On the other hand, setting the gain unnecessarily low risks missing low intensity returns.
The present invention is directed to resolving, or at least reducing, one or all of the problems mentioned above.
The invention, in its various aspects and embodiments, includes an optical system and a method for automatically controlling the gain of a receiver in an optical system. The optical system comprises an optical receiver, a pulse capture unit, and an automatic gain control. The pulse capture unit includes a capture unit capable of capturing an optical signal received by the optical receiver; and, a process unit capable of processing the captured optical signal. The automatic gain control is capable of controlling the gain of the optical receiver responsive to the content of the processed optical signal. The method comprises comparing the intensity of a returned pulse to a predetermined value; and controlling the gain of an optical detector responsive to the comparison.
The invention may be understood by reference to the following description taken in conjunction with the accompanying drawings, in which like reference numerals identify like elements, and in which:
While the invention is susceptible to various modifications and alternative forms, the drawings illustrate specific embodiments herein described in detail by way of example. It should be understood, however, that the description herein of specific embodiments is not intended to limit the invention to the particular forms disclosed, but on the contrary, the intention is to cover all modifications, equivalents, and alternatives falling within the spirit and scope of the invention as defined by the appended claims.
Illustrative embodiments of the invention are described below. In the interest of clarity, not all features of an actual implementation are described in this specification. It will of course be appreciated that in the development of any such actual embodiment, numerous implementation-specific decisions must be made to achieve the developers' specific goals, such as compliance with system-related and business-related constraints, which will vary from one implementation to another. Moreover, it will be appreciated that such a development effort, even if complex and time-consuming, would be a routine undertaking for those of ordinary skill in the art having the benefit of this disclosure.
The present invention uses a median-value approach to the gain-control mechanism of an optical system. Statistically, using the median is more robust than averaging or single-sample techniques. Other methods of determining the median of a large set values are very computationally intensive that the present invention greatly reduces. Only one comparison computation is required per input sample. Each one of a sequential set of input samples is compared (once) against the median set-point and a counter increments the number of “greater than” results. After a predetermined number of comparison cycles, the counter value represents how close the gain-control mechanism has achieved the desired median. If the counter is at half maximum value, the median has been achieved. Any deviation from this “half value” is proportional to the error. The gain-control mechanism then uses this deviation to “close the loop” and force the error to approach zero over the course of several comparison cycles. This process can provide smooth adaptive control as both external and internal conditions change.
The maximum gain is also typically, though not in all embodiments, limited by an active noise measurement technique. This technique keeps the Constant False Alarm Rate (“CFAR”) due to detector and background random noise from exceeding a predetermined level. The technique is adaptive to changing conditions and allows the maximum gain possible when signals are weak. Statistically, random noise (per time increment) is equally likely during any period of measurement. Thus the level of random noise can be determined during a period when no return signal is expected. The number of noise occurrences in several periods are accumulated and then evaluated. If and when that number equals or exceeds an allowable CFAR limit, the gain is prohibited from increasing and may be slightly decreased.
In the illustrated embodiment, the LADAR transceiver 110 continually sends input data in the form of an optical signal 350 to the PCE 115. This input data is sometimes core data, e.g., the optical signal 350 is the collected return pulse 140 (shown in
To help separate these conditions, and for other reasons, the PCE 115 employs a timing mechanism illustrated in
The times and widths of the time periods T1, T2 are determined by the operational parameters of the LADAR system 100. The location and width of the time period T1 is defined by some expectation of the flight time for the emitted pulse 125 to reflect back to the LADAR transceiver 110. For instance, one might assume that only targets greater than 100 m but less than 2 km of the LADAR transceiver 110 will be detected and identified. This assumption, given the speed of light, will yield the times tre and trd. The width of the time period T2 may be selected on some arbitrary basis, but a width equal to the width of the time period T1 is employed in the illustrated embodiment. The time period T3 between the time periods T1, T2 also may be arbitrarily selected, provided that the sum of T1, T2, and T3 is less than the period of the laser firing clock 410. However, in the illustrated embodiment, the time period T3 is set at least as long as it takes the capture and process unit 330 to process any data received in the time period T1. Also, the time period T2 preferably ends after the capture and process unit 330 operates on the incidental data as is described further below.
Turning now to
More particularly, when the range gate (not shown) is enabled during the period T1, shown in
When the noise gate (not shown) is enabled during the period T2, shown in
The content of the up/down counter 510 is converted to an analog signal by the A/D converter 540. The analog count is then used by the attenuator 550 to attenuate the 500 Vdc power supplied to the detector array 310 to produce the detector array gain signal 395. The attenuator 550 is implemented in one particular embodiment using field effect transistor (“FET”) technology, but any suitable technology may be employed.
To further an understanding of the invention, one particular implementation of the LADAR system 100 shall now be discussed. In this discussion, for this particular implementation:
More particularly,
Output signals (not shown) from the pumping laser 612 are transmitted through an input lens 611 and through a fiber optic bundle 616 which has sufficient flexibility to permit scanning movement of the seeker head 110 during operation. The output beam 618 generated by solid state laser 614, in the present embodiment, is successively reflected from a first and a second turning, or folding, mirror 620 and 622 to a beam expander 624. The beam expander 624 comprises a series of (negative and positive) lenses adapted to expand the diameter of the beam 618 to provide an expanded beam 625, suitably by an 8:1 ratio, while decreasing the divergence of the beam 618 to the expanded beam 625.
The expanded beam 625 is next passed through a beam segmenter 626 for dividing the expanded beam 625 into a plurality of beam segments 627, conceptually represented by a single beam segment 627. The beam segments 627 are arrayed on a common plane, initially overlapping, and diverging in a fan shaped array. The beam segmenter 626 preferably segments the beam into 8 separate but overlapping beam segments 627. The divergence of the segmented beams 627 is not so great as to produce separation of the beams within the optical system, but preferably is sufficiently great to provide a small degree of separation at the target, as the fan-shaped beam array is scanned back and forth over the target.
The segmented beams 627 are then reflected from a third turning mirror 628, passed through a central aperture 630 of an apertured mirror 632, and subsequently reflected from a scanning mirror 634. The segmented beams 627 are reflected from the scanning mirror 634 in a forward direction relative to the LADAR system 100, represented by the arrow 635. The scanning mirror 634 is pivotally driven by a scanning drive motor 636 operable to cyclically scan the array of beam segments 627 for scanning the field of view 135, shown in
An a focal, Cassigrainian telescope 638 further expands and directs the emitted beam. The telescope 638 includes a forwardly facing primary mirror 640 and a rearwardly facing secondary mirror 642. A protective outer dome 644 of a suitable transparent plastic or glass is mounted forward of the secondary mirror 642. A lens structure 646 is mounted in coaxial alignment between the primary mirror 640 and the scanning mirror 634, and an aperture 648 is formed centrally through the primary mirror 640 in alignment with the lens structure 646.
The transmitted beam segments 627 reflected from the scanning mirror 634 are directed through the lens structure 46 for beam shaping, directed through the aperture 648 formed centrally through the primary mirror 640, reflected from the secondary mirror 42 spaced forwardly of the primary mirror 640, and then reflected off the primary mirror 640 and out through the transparent dome 644. The resultant emitted pulse 125 is a fan shaped array scanned about an axis parallel to its plane. The beam segments 627 of the emitted pulse 125 are in side-by-side orientation mutually spaced by a center-to-center distance of twice their diameters.
The emitted pulse 125 is reflected as described above relative to
The collected return pulse 140 then passes through condensing optics 654 for focusing the collected return pulse 140, and then a fourth turning mirror 656 re-directs the collected return pulse 140 toward a focusing lens structure 658 adapted to focus the collected return pulse 140 upon the receiving ends 660 of a light collection fiber optic bundle 662. The opposite ends of each optical fiber 662 are connected to illuminate diodes 664 in the detector array 310. Note that the detector array 310 actually comprises a portion of the PCE 115, but is presented in this discussion of the LADAR transceiver 110 for clarity.
The detector array 310 converts the laser light signals of the collected return pulse 140 to electrical signals that are conducted to the remainder of the PCE 115, first shown in
One particular implementation of the LADAR transceiver 110 splits a single 0.2 mRad 1/e2 laser pulse into septets with a laser beam divergence for each spot of 0.2 mRad with beam separations of 0.4 mRad. The fiber optical array 310, shown in
Note that alternative embodiments may employ LADAR transceivers other than the LADAR transceiver 110 discussed above. Other suitable transceivers include those disclosed in, inter alia, the following patents:
More particularly, from the standpoint of the invention, the collected return pulse 670 is digitized and stored and a detailed analysis that utilizes many time samples is performed. This analysis “slides” a template across the stored sequence of samples to find the best match. The location of this best match is proportional to the range of the captured pulse while the strength of the match is related to its intensity. The template averages or convolves many samples together to improve the signal to noise ratio and to find the center of the return pulse. Using this method, signal amplitude variations may be ignored. An appropriate template can also be used for second-pulse logic to extract secondary returns even if the later pulse is partially overlapped by a stronger primary return. This analysis yields a data set representing the shape of the returned pulse 140. This shape is compared to that of the emitted pulse 120 to determine flight time of the pulses 120, 140 to and from the target. This method avoids certain limitations experienced in prior-art, analog edge detection systems relating to power, range, or frequency considerations.
Returning to
Still referring to
As previously mentioned, the detector array 310 comprises a plurality of photodiodes 664. In the illustrated embodiment, the photodiodes 664 are avalanche photodiodes (“APD”). However, as will be appreciated by those in the art having the benefit of this disclosure, a wide variety of detector technologies may instead be employed to implement the detector array 310. Any such suitable detector technology may be employed, and the invention is not limited by this aspect of the implementation. The optical signals collected by the photodiodes 664 are then amplified by the post-amplifiers 765 and output to the threshold unit 320.
The threshold unit 320 converts the analog, collected return pulse 140 signal to a digital signal using a 1 GHz flash converter process. A bank of voltage comparators (not shown) is employed, and comparison is accomplished by first converting each pulse signal to a string of digital signals. Each portion of the collected return pulse 140 equals the instantaneous amplitude of the signal received at that moment. In the illustrated embodiment, the threshold unit 320 employs a comparison circuit (not shown) comprising seven individual, nonlinear comparators (not shown). The comparators are preferably flash converters ganged together and spaced apart in their threshold in a logarithmic function, between 30 mV and 1 V, based on expected return. The collected return pulse 140 is fed to all seven comparators at once, but each has a different reference voltage 766, and levels being spaced in logarithmic intervals over the expected voltage range. Starting at the lower level, all the analog comparators with digital outputs operate like an operable amplifier with no feedback. At every clock, the highest comparator turns on. The threshold unit 320 outputs the resultant continuous digital representation 370 of the optical signal 350.
Note that more than seven comparators can be used to increase the amplitude resolution and reduce the effects of sampling jitter and noise. Note further that the values of the reference voltages 766 for the multi-level comparison by the threshold unit 320 are set by predetermined values stored in the register 768. However, this is only one approach to setting these values. For instance, the values could be stored in the control registers 770, or even the RAM 730. The control registers 770 are used to store operational parametrics. These values may be loaded prior to use of the LADAR system 100 through the test port 772, but, again, alternative techniques may be employed.
The capture and process unit 330 includes the capture unit 720, RAM 730, and process unit 740 capture the collected return pulse 140 and process it. The capture unit 720 samples the digitized representation of the collected return pulse 740 output by the threshold unit 320 at 500 MHz. The capture unit 720 converts the sampled signal 370 into a 3-bit word (or, “thermometer code”) proportional to the peak of the collected return pulse 140, and stores the coded samples in the RAM 730. The process unit 740 then performs the detailed analysis mentioned above on the data samples stored in the RAM 730. The result of this analysis is output to the input/output (“I/O”) unit 774, which conditions the results to produce and output the three-dimensional data 380.
The capture unit 720 comprises a gate array and is better shown in
A 4:1 time demultiplexer 820 is provided which, in operation, allows eight nanoseconds for the encoding of a signal. From the capture unit 720, four three-bit samples are then stored in the RAM 730. Thus, the capture unit 720 samples the status or state of the bank of comparators in the threshold unit 320 every two nanoseconds to determine how many of the comparators are turned on, assigns a digital word (0, 1, 2 through 7) indicating that determination, and stores the digital word in the RAM 730.
In the illustrated embodiment, the capture unit 720, as well as some other aspects of the PCE 115, is implemented in a field programmable gate array (“FPGA”) 780. Current FPGA technology is not capable of operating at 1 GHz frequencies, unlike the emitter-coupled logic (“ECL”) of the prior art. Thus, the illustrated embodiment employs a multiphase clock generator 760 that generates a multiphase clock signal from an input clock signal, each phase of which is used to by the capture unit 720 to time a respective sampling. The illustrated embodiment uses this multiphase clock technique to sample digitized, collected return pulse 140 at a rate effectively higher than the basic FPGA clock rate of 125 MHz.
Consider, for instance, the particular implementation shown in
Returning to
The convolution circuit 1110 includes a matched filter 1112 and, in some embodiments, the optional linearize circuit 1114. The linearize circuit 1114 strips out the non-linearity introduced by the non-linear threshold unit 320. The matched filter 1112 may be any FIR filter known to the art. The matched filter 1112 is loaded with a set of coefficients representative of the expected shape of the return pulse 140. This set of coefficients defines the template discussed above. The convolution circuit 1110 produces evaluation numbers indicative of the degree of correlation between the template and the return pulse 140.
The design of convolution circuits, e.g., the convolution circuit 1110, is well-known in the art. Conventional convolution circuits feed the samples serially into the filter thereof, each sample being fed one at a time. In this conventional approach, the template is shifted across the stored sequence in discrete steps defined by the sampling rate at which the analog return pulse is digitized. Each discrete step is no wider or narrower than an individual sample and the resolution of any measurement obtained therefrom is determined by the sampling rate in the analog-to-digital conversion.
In one particular embodiment, the convolution circuit 1110 effectively improves the sampling rate at which the return pulse is digitized. The convolution circuit 1110 does so by “interpolating” between samples. For an R:1 interpolation, where R>1, each sample is clocked out of the buffer 222 and into the convolution circuit 1110 R times before clocking out the next sample so that each sample is fed into the convolution R times.
Thus, the convolution circuit 1110 repeatedly convolves each one of at least a portion of the buffered samples R times, wherein R>1. This convolution technique may also be conceptualized as shifting the template in steps smaller than the input samples such that a correlation determination can be made at points in between the discrete samples. This convolution technique therefore produces an effective sampling rate potentially much higher than the actual sampling rate without directly impacting the data acquisition. Consequently, the resolution of the range extracted therefrom is improved by a factor of R.
The peak detect circuit 1120 processes the evaluation numbers from the convolution circuit 1110 to determine the point in time where a “best match” occurs between the return pulse and the template. “Best match” is defined, in this context, as the set of samples among those filtered whose correlation with the template is highest. By identifying the portion of the sampled return signal that best matches the stored template, the peak detect circuit 1120 effectively determines the time at which the return pulse 140 was received.
Thus, the peak detect circuit 1120 detects the center of energy for the return pulse 140 from the convolution results output by the convolution circuit 1110. Technically, as those in the art having the benefit of this disclosure will appreciate, the peak detect circuit 1120 detects the peak of the processed, digitized samples, which theoretically represents the peak of the return signal 1120. However, in practice, this is not always the case as the data may be corrupted or polluted. Thus, the peak of the processed samples indicates the return pulse's center of energy, from which the time at which the pulse was received may be more accurately determined.
As noted above, any convolution circuit including a matched filter known to the art can be employed to perform the convolution of the samples with the template, provided it is modified to clock each sample R times to perform an R:1 interpolation. That is, any convolution circuit known to the art may be used to implement the convolution circuit 1110. However, in the interest of completeness, two implementations for the convolution circuit 1110 are disclosed.
Turning now to the first implementation of the convolution circuit 1110,
In the second implementation illustrated in
Turning now to
Preferably, a double-accumulator is implemented using a set of D-A coefficients derived from the input filter coefficient stream (“FCS”), e.g., the FCS in
The weighting technique can be accomplished by multiplying each D-A coefficient by a separate input sample, as will be discussed relative to
Such a double-accumulator can be implemented in a variety of circuits. For example, a register-based double accumulator may be implemented using a shift register to sequentially move input data across the inputs to a plurality of multipliers. The multipliers are used to multiply the input data by selected D-A coefficients. The products are summed together and provided to a first accumulator. The first accumulator provides its output to the input of a second accumulator. The second accumulator provides the result.
This particular double accumulator implementation is, as discussed above, deployed in a RAM-based convolver. The RAM 730, shown in
More particularly, a D-A convolver circuit is constructed from coefficients derived from the filter coefficient stream (“FCS”). These coefficients are referred to as “D-A coefficients.” Referring to
The D-A coefficients are preferably ascertained from the second derivative of the FCS.
X′n=( xn)/(
t)=xn−xn+1
X″n=( xn′)/(
t′)=xn−xn″+1
The resulting values are the D-A coefficients.
D-A coefficients are readily ascertained from most any function expressed as a series of line segments. One D-A coefficient is designated for each point where two line segments meet. The value of a D-A coefficient is equal to the change in slope (second derivative) from the first line segment to the second. Examples of this method are shown in
Referring first to
Returning to
Still referring to
More particularly,
As an example for a specific DSP application concerning a LASER radar, the clock line 2610 provides a clock at a rate of 83.3 MHz, with a D-A coefficient designated for the input function every 4 nanoseconds.
While three multipliers 1803, 1804 and 1805 are shown, the multipliers 1803 and 1804 are unnecessary and can be bypassed because they are arranged to multiply by one. Moreover, a register performing a simple binary shift operation can replace the multiplier 1804 because its function, multiplying by a factor of two, is effected by a single binary shift. Such circuitry reduction is common, expected and considered to be understood in the illustrated embodiments herein because, by their nature, D-A coefficients are generally small numbers.
The matched filter 1114, first shown in
A RAM-based convolver may also be used to implement the matched filter 1114.
Returning now to
The output of the capture and process unit 330 includes the pulse intensity and pulse detect data input to the AGC 340 as discussed above relative to
Still referring to
Turning now to the ATR System 120,
Returning to
Generally, the preprocessing (at 3352) is directed to minimizing noise effects, such as identifying so-called intensity dropouts in the converted three-dimensional data set 380, where the range value of the data is set to zero. Noise in the converted three-dimensional data set 380 introduced by low signal-to-noise ratio (“SNR”) conditions is processed so that performance of the overall LADAR system 100 is not degraded. In this regard, the three-dimensional data set 380 is used so that absolute range measurement distortion is minimized, edge preservation is maximized, and preservation of texture step (that results from actual structure in objects being imaged) is maximized.
In general, detection (at 3354) identifies specific regions of interest in the three-dimensional data set 380. The detection (at 3354) uses range cluster scores as a measure to locate flat, vertical surfaces in an image. More specifically, a range cluster score is computed at each pixel to determine if the pixel lies on a flat, vertical surface. The flatness of a particular surface is determined by looking at how many pixels are within a given range in a small region of interest. The given range is defined by a threshold value that can be adjusted to vary performance. For example, if a computed range cluster score exceeds a specified threshold value, the corresponding pixel is marked as a detection. If a corresponding group of pixels meets a specified size criteria, the group of pixels is referred to as a region of interest. Regions of interest, for example those regions containing one or more targets, are determined and passed to a segmenter for further processing.
Segmentation (at 3356) determines, for each detection of a target 130 (shown in
Feature extraction (at 3358) provides information about a segmentation (at 3356) so that the target 130 and its features in that segmentation can be classified. Features include, for example, orientation, length, width, height, radial features, turret features, and moments. The feature extraction (at 3358) also typically compensates for errors resulting from segmentation (at 3356) and other noise contamination. Feature extraction (at 3358) generally determines a target's three-dimensional orientation and size and a target's size. The feature extraction (at 3358) also distinguishes between targets and false alarms and between different classes of targets.
Classification (at 3360) classifies segmentations to contain particular targets, usually in a two stage process. First, features such as length, width, height, height variance, height skew, height kurtosis, and radial measures are used to initially discard non-target segmentations. The segmentations that survive this step are then matched with true target data stored in a target database. The data in the target database, for example, may include length, width, height, average height, hull height, and turret height to classify a target. The classification (at 3360) is performed using known methods for table look-ups and comparisons.
Data obtained from the segmentation (at 3356), the feature extraction (at 3358), and the classification (at 3360) may, in some embodiments, be displayed in one of a variety of user-selectable formats. Typical formats include a three-view commonly used by armed forces to identify targets during combat, a north reference plan view, or a rotated perspective. These display options available to the operator, either local or remote, are based on the three-dimensional nature of the LADAR image. The results of the feature extraction (at 3358) provide target information including orientation, length, width and height. The target image can be displayed from any perspective, independent of the sensor perspective, and the operator can select one of the several display formats that utilize the adjustable perspective.
The data obtained from the segmentation (at 3356) is then used in identifying, or “recognizing,” the target. One suitable method for this identification is disclosed in:
Many aspects of the processing by the ATR system 120 are software-implemented, especially the method 3300 in
It should be borne in mind, however, that all of these and similar terms are to be associated with the appropriate physical quantities and are merely convenient labels applied to these quantifies. Unless specifically stated or otherwise as may be apparent, throughout the present disclosure, these descriptions refer to the action and processes of an electronic device, that manipulates and transforms data represented as physical (electronic, magnetic, or optical) quantities within some electronic device's storage into other data similarly represented as physical quantities within the storage, or in transmission or display devices. Exemplary of the terms denoting such a description are, without limitation, the terms “processing,” “computing,” “calculating,” “determining,” “displaying,” and the like.
Note also that the software implemented aspects of the invention are typically encoded on some form of program storage medium or implemented over some type of transmission medium. The program storage medium may be magnetic (e.g., a floppy disk or a hard drive) or optical (e.g., a compact disk read only memory, or “CD ROM”), and may be read only or random access. Similarly, the transmission medium may be twisted wire pairs, coaxial cable, optical fiber, or some other suitable transmission medium known to the art. The invention is not limited by these aspects of any given implementation.
The operation of this particular implementation of the LADAR transceiver 110 in the LADAR system 100 is conceptually illustrated in
As the LADAR transceiver 110 scans the field of view 220, shown in
As described with respect to
During the period T1, the AGC 340, shown in
Returning to
However, at tne, the period T2 begins with the noise gate enable. The PCE 115 assumes that any “pulse,” e.g., the noise event 3505, detected during the period T2 is generated from noise since it expects all return pulses 140 to be detected in the period T1. It is expected that a noise event will only be detected relatively rarely. However, when a noise event 3505 is detected, the AGC 340 decrements the counter 510, shown in
Thus, in another aspect, the invention includes a method 3600, illustrated in
In the context of the illustrated embodiment, the invention further includes a method 3700, illustrated in
This concludes the detailed description. The particular embodiments disclosed above are illustrative only, as the invention may be modified and practiced in different but equivalent manners apparent to those skilled in the art having the benefit of the teachings herein. For instance, the LADAR transceiver may, in alternative embodiments, emit a continuous, as opposed to pulsed, beam. Furthermore, no limitations are intended to the details of construction or design herein shown, other than as described in the claims below. It is therefore evident that the particular embodiments disclosed above may be altered or modified and all such variations are considered within the scope and spirit of the invention. Accordingly, the protection sought herein is as set forth in the claims below.
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