Switch-capacitor techniques for level-shifting

Abstract

In one embodiment, a circuit comprises at least first and second circuit stages, at least one level shifting circuit, and a control circuit. The first circuit stage is configured and arranged to produce a reference voltage at the at least one first output during each first phase of at least first and second phases, and to produce an output signal at the at least one first output that is responsive to an input signal at the at least one first input during each second phase of the at least first and second phases. The at least one level shifting circuit comprises at least one capacitor and at least one switch and is coupled between the first circuit stage and the second circuit stage. The control circuit is configured to control the level shifting circuit such that, during each first phase, respective plates of the at least one capacitor are connected to the at least one first output of the first circuit stage and a source of a substantially constant voltage so as to allow the at least one capacitor to be charged to a level-shift voltage equal to a difference between the substantially constant voltage and the reference voltage, and such that, during each second phase, the respective plates of the at least one capacitor are connected to the at least one first output and the at least one second input to thereby introduce the level-shift voltage across the at least one capacitor as an offset voltage therebetween.

Description

This application claims the benefit of U.S. Provisional Application Ser. No. 60/813,533, filed on Jun. 14, 2006, the entire contents of which is incorporated herein by reference.

BACKGROUND

One of the major difficulties in moving towards higher A/D conversion rates is the decreased available settling time for amplifiers. In older process generation designs, linear behavior dominates amplifier settling. Due to higher transition frequency (f_T) transistors in deep sub-micron complementary metal oxide semiconductor (CMOS) layouts, slew behavior can dominate.

Amplifiers that employ “push-pull,” or “class AB,” topologies can efficiently achieve high-speed settling while driving large capacitive loads. FIGS. 1 and 2 are diagrams of prior art circuits employing, respectively, a common-source push-pull topology and a common-drain push-pull topology. An advantage of push-pull amplifiers like those shown is that a large transient current can be made available without consuming a large standing current. Such push-pull amplifiers can be made efficient by introducing a level-shift between the nominal input voltage and the desired gate voltages. In the circuits of FIGS. 1 and 2, voltage sources 102 and 104 are employed to introduce bias voltages V_{BIAS, P} and V_{BIAS, N}, respectively, between the input node 106 and the gates of the amplifier's complementary transistors. As illustrated in FIG. 3, this type of level-shifting can also be applied to other amplifier topologies, such as a level-shifted Class A amplifier.

Active level-shifting between the input voltage and gate voltages has been proposed in Gray, P. et al., Analysis and Design of Analog Integrated Circuits, New York: John Wiley, 2001, p. 364, which is incorporated herein by reference in its entirety. In CMOS technologies, switched-capacitor level shifting, such as that illustrated in FIG. 4, has also been used. Examples of such uses are described in Allen, P. and Holberg, D., CMOS Analog Circuit Design, New York: HRW, 1987, pp. 509-511; Hosticka, B., “Dynamic CMOS Amplifiers,” IEEE J. Solid-State Circuits, vol. SC-15, pp. 887-894, October 1980; Palmisano, G. and Pennisi, S., “Dynamic Biasing for True Low-Voltage CMOS Class AB Current-Mode Circuits,” IEEE Trans. on Circuits and Systems, vol. 47, pp. 1569-1575, December 2000; Fayomi, C. J. B. et al, “A design strategy for a 1-V rail-to-rail input/output CMOS opamp,” 2001 Int. Symposium on Circuits and Systems, vol. 1, pp. 639-642, each of which is incorporated herein by reference in its entirety.

In the example of FIG. 4, charged capacitors 402, 404 are selectively connected between the input node 406 and the gates of complementary transistors 408, 410. Switched-capacitor level-shifting thus allows direct connections between the input and high impedance nodes (transistor gates in the illustrated example). Compared to active level-shifting, switched-capacitor level-shifting is power efficient and eliminates parasitic poles in the signal path.

In order to employ capacitive level-shifting, the proper charge needs to be applied to the level-shift capacitors 402, 404. One previously used technique for applying such charge is shown in FIG. 5. In this configuration, a charge-refreshing capacitor C_REF is used to supply the needed charge on a level-shift capacitor C_LS. In particular, during a first phase Φ₁, switches 502, 504 are closed and switches 505, 507 are opened, thus allowing charge from the charge-refreshing capacitor C_REF to be transferred to level-shift capacitor C_LS. During a second phase Φ₂, the switches 502, 504 are opened and the switches 505, 507 are closed, so that the voltage on the level-shift capacitor C_LS is introduced between the input node 510 and the gate of NMOS transistor 512, and the charge-refreshing capacitor C_REF is recharged when its plates are connected to a reference voltage node 506 and a bias voltage node 508.

SUMMARY OF THE INVENTION

According to one aspect of the present invention, a method involves providing a circuit comprising at least first and second circuit stages and a first level-shift capacitor, each of the first and second circuit stages comprising at least one input, at least one output, and at least one signal processing element coupled therebetween. At least one signal is received that defines at least first and second phases. A first circuit node is provided having a first substantially constant voltage thereon at least during the first and second phases, wherein the first substantially constant voltage remains substantially constant when a significant amount of charge is transferred between the first circuit node and the first level shift capacitor during a first phase, and a second circuit node is provided having a first reference voltage thereon at least during the first phases. During each first phase, the circuit is configured such that respective plates of the first level-shift capacitor are connected to the first and second circuit nodes, thereby allowing the first level-shift capacitor to charge to a level-shift voltage equal to a difference between the first substantially constant voltage and the first reference voltage. During each second phase, the circuit is configured such that the respective plates of the first level-shift capacitor are connected to a first output of the first circuit stage and a first input of the second circuit stage, without causing the first level-shift capacitor to be connected in parallel with another capacitor with which it was not connected in parallel during a preceding first phase, thereby introducing the voltage across the first level-shift capacitor as an offset voltage between the first and second circuit stages.

According to another aspect, a method involves providing a circuit comprising at least first and second circuit stages and a first level-shift capacitor, wherein each of the first and second circuit stages comprises at least one input, at least one output, and at least one signal processing element coupled therebetween, and wherein the at least one output of the second circuit stage is connected to a load. At least one signal is received that defines at least first and second phases. A first circuit node is provided having a first substantially constant voltage thereon at least during the first phases, wherein the first substantially constant voltage remains substantially constant when a significant amount of charge is transferred between the first circuit node and the first level-shift capacitor during a first phase, and wherein the at least one output of the second circuit stage remains connected to the load when the first substantially constant voltage is established on the first node during the first phases. A second circuit node is provided having a first reference voltage thereon at least during the first phases. During each first phase, the circuit is configured such that respective plates of the first level-shift capacitor are connected to the first and second circuit nodes, thereby allowing the first level-shift capacitor to charge to a level-shift voltage equal to a voltage difference between the first substantially constant voltage and the first reference voltage. During each second phase, the circuit is configured such that the respective plates of the first level-shift capacitor are connected to a first output of the first circuit stage and a first input of the second circuit stage, without causing the first level-shift capacitor to be connected in parallel with another capacitor with which it was not connected in parallel during a preceding first phase, thereby introducing the voltage across the first level-shift capacitor as an offset voltage between the first and second circuit stages.

According to another aspect, a circuit comprises at least first and second circuit stages, at least one level shifting circuit, and a control circuit. The first circuit stage comprises at least one first input, at least one first output, and at least one first signal processing element coupled therebetween, and is configured and arranged to produce a reference voltage at the at least one first output during each first phase of at least first and second phases, and to produce an output signal at the at least one first output that is responsive to an input signal at the at least one first input during each second phase of the at least first and second phases. The second circuit stage comprises at least one second input, at least one second output, and at least one second signal processing element coupled therebetween. The at least one level shifting circuit comprises at least one capacitor and at least one switch and is coupled between the first circuit stage and the second circuit stage. The control circuit is configured to control the level shifting circuit such that, during each first phase, respective plates of the at least one capacitor are connected to the at least one first output of the first circuit stage and a source of a substantially constant voltage so as to allow the at least one capacitor to be charged to a level-shift voltage equal to a difference between the substantially constant voltage and the reference voltage, and such that, during each second phase, the respective plates of the at least one capacitor are connected to the at least one first output and the at least one second input to thereby introduce the level-shift voltage across the at least one capacitor as an offset voltage therebetween.

According to another aspect, a method involves providing a circuit comprising first and second circuit stages, and first, second, third, and fourth level-shifting capacitors, wherein each of the first and second circuit stages comprises at least one input, at least one output, and at least one signal processing element coupled therebetween, and wherein the second circuit stage comprises first and second differential inputs. At least one signal is received that defines at least first and second phases. First and second circuit nodes are provided having substantially constant voltages thereon at least during the first phases, and third and fourth circuit nodes are provided having reference voltages thereon at least during the first phase. During each first phase, the circuit is configured such that (1) respective plates of the first level-shift capacitor are connected to the first and third circuit nodes, (2) respective plates of the second level-shift capacitor are connected to the second and fourth voltage nodes, (3) respective plates of the third level-shift capacitor are connected to an output of the first circuit stage and the first differential input of the second circuit stage, and (4) respective plates of the fourth level-shift capacitors are connected to an output of the first circuit stage and the second differential input of the second circuit stage. During each second phase, the circuit is configured such that (1) respective plates of the third level-shift capacitor are connected to the first and third circuit nodes, (2) respective plates of the fourth level-shift capacitor are connected to the second and fourth voltage nodes, (3) respective plates of the first level-shift capacitor are connected to an output of the first circuit stage and the first differential input of the second circuit stage, and (4) respective plates of the second level-shift capacitors are connected to an output of the first circuit stage and the second differential input of the second circuit stage.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a diagram of a prior art amplifier circuit employing a class AB common-source topology;

FIG. 2 is a diagram of a prior art amplifier circuit employing a class AB common-drain topology;

FIG. 3 is a diagram of a prior art amplifier circuit employing a level-shifted class A common-source topology;

FIG. 4 is a diagram of a prior art amplifier circuit employing a capacitive level-shifted class AB common-drain topology;

FIG. 5 is a diagram of a prior art amplifier circuit employing a switched-capacitor technique for biasing a level-shift capacitor in a class A common-source topology;

FIGS. 6 and 7 are timing diagrams illustrating examples of signals that may be used to control switches in the various embodiments described herein;

FIG. 8 is a diagram illustrating an example of an inventive switched-capacitor circuit and technique for biasing a pair of level-shift capacitors in a differential amplifier circuit employing a class A common-source topology;

FIG. 9 is a diagram illustrating an example of an inventive switched-capacitor circuit and technique for biasing four separate level-shift capacitors in a differential amplifier circuit employing a class AB common-source topology;

FIG. 10 is a diagram illustrating an example of an inventive switched-capacitor circuit and technique for biasing a level-shift capacitor disposed between two stages of a multiple-stage, single-ended amplifier circuit employing a class A common-source topology wherein a reference voltage for the level-shift capacitor is provided by the first amplifier stage during one operational phase;

FIG. 11 is a diagram illustrating an example of an inventive switched-capacitor circuit and technique for biasing a pair of level-shift capacitor disposed between two stages of a differential multiple-stage amplifier circuit employing a class A common-source topology wherein reference voltages for the level-shift capacitors are provided by the first amplifier stage during one operational phase;

FIG. 12 is a diagram illustrating an example of an inventive switched-capacitor circuit and technique for biasing four separate level-shift capacitors disposed between two stages of a differential multiple-stage amplifier circuit employing a class AB common-source topology wherein a reference voltage for the level-shift capacitor is provided by the first amplifier stage during one operational phase;

FIG. 13 is a diagram illustrating an example of an inventive switched-capacitor circuit and technique that involves the swapping of level-shift capacitors in a differential amplifier circuit employing a class A common-source topology;

FIG. 14 is a diagram illustrating an example of an inventive switched-capacitor circuit and technique that involves the swapping of level-shift capacitors in a differential amplifier circuit employing a class AB common-source topology;

FIG. 15 is a diagram illustrating an example of alternative circuit that may be employed in either of the embodiments of FIGS. 13 and 14, in which four, rather than two, level-shift capacitors are employed to level shift respective input nodes of an amplifier or other circuit; and

FIG. 16 is a timing diagram illustrating examples of signals that may be used to control various switches in the circuit of FIG. 15.

DETAILED DESCRIPTION

A problem with the prior art technique illustrated in FIG. 5 is that certain disturbances in the charge on level-shift capacitor C_LS may not be completely fixed in the next phase. That is, during each phase Φ₁, the closing of the switches 502, 504 and opening of the switches 505, 507 merely allows the charges on capacitors C_REF and C_LS to balance out. That means that the voltage on the level-shift capacitor C_LS can be altered only incrementally by an amount dependent on the ratio of the two capacitance values. It can thus take many clock cycles in order for the charge-refreshing capacitor C_REF to adequately correct any errors in the charge on the level-shift capacitor C_LS. The time required for disturbance recovery is thus a function of the ratio between the values of the charge-refreshing capacitor C_REF and the level-shift capacitor C_LS, as well as the required accuracy.

This slow recovery can be problematic in high-speed amplifiers, and can be particularly troublesome in applications where the recovery time is longer than the time constant of the signals being processed. Furthermore, if the disturbance is signal dependent, such as feedthrough from the output node through the gate-drain overlap capacitance, such a circuit can exhibit a memory effect from one clock cycle to the next.

Several different and improved circuits and techniques for biasing one or more level-shift capacitors are disclosed herein. In some embodiments, use of these new techniques can allow the level-shift capacitor(s) to recover from any disturbance within one clock cycle.

Any of a number of clocking schemes may be employed to establish the various phases and control the various switches discussed herein. A few examples of suitable clocking techniques are shown in FIGS. 6 and 7. As shown in FIG. 6, in some embodiments, a single clock signal CLK may be used to establish non-overlapping phases Φ₁ and Φ₂ and to control all of the switches in the circuit. In such embodiments, for example, switches that are closed in response to a logical low signal may be employed as the phase Φ₁ switches, and switches that are closed in response to a logical high signal may be employed as the phase Φ₂ switches. Alternatively, as shown in FIG. 7, separate clock signals SC1 and SC2 may be employed to control the phase Φ₁ switches and the phase Φ₂ switches, respectively, in which case switches that are closed in response to the same logical signal level may be used throughout the circuit. In some embodiments, phases in addition two phases Φ₁ and Φ₂ may also be established, and the two described phases Φ₁ and Φ₂ may be a subset of a larger number of phases employed in a system.

FIG. 8 illustrates one example of an inventive level-shifting circuit 802. In the example shown, the level-shifting circuits 802a, 802b are used to provide level shifts for the differential inputs of a class A common-source amplifier 804. Input nodes 816a, 816b may, for example, be connected to respective outputs of a preceding amplifier stage (not shown in FIG. 8). As discussed in more detail below, however, the level-shifting circuit 802, as well as the other level-shifting circuits disclosed herein, may alternatively be used in any of a number of other environments to introduce a level shift to any of a number of other devices, and the invention is not necessarily limited to any particular application.

In the example shown, during each phase Φ₁, switches 810a, 810b are opened so that level-shift capacitors C_LSA and C_LSB are disconnected from the positive and negative input nodes 816a, 816b, and the switches 812a, 812b, 814a, 814b are closed so that the plates of the level-shift capacitors C_LSA and C_LSB are connected to reference voltage nodes 806a, 806b and bias voltage nodes 808a, 808b. The nodes 806a, 806b, 808a, 808b may, for example, be connected to outputs of voltage sources that generate substantially constant voltages regardless of the loads attached thereto and the amount of charge transferred to or from the level-shift capacitors C_LSA, C_LSB. The nodes 806a, 806b, 808a, 808b may either be connected to separate voltage sources or to a shared voltage source, depending on the layout and desired characteristics of the circuit. Connecting the level-shift capacitors C_LSA, C_LSB across the nodes 806a, 806b, 808a, 808b thus sets the proper charge on the level-shift capacitors C_LSA, C_LSB during the phase Φ₁. During each phase Φ₂, the switches 810a, 810b are closed and the switches 812a, 812b, 814a, 814b are opened, so that level-shift capacitors C_LSA, C_LSB are connected back to the input nodes 816a, 816b, and act as batteries that force the correct bias voltages on the gates of NMOS transistors 818a, 818b of the differential amplifier 804 for inputs that are equal to the reference voltages.

Accordingly, during each phase Φ₁, the charge on each of the level-shift capacitors C_LSA, C_LSB can be completely restored to the intended value, and, if an error is introduced onto either of the level-shift capacitors C_LSA, C_LSB during a phase Φ₂, it will be removed during the subsequent phase Φ₁ and will not affect the following phase Φ₂.

FIG. 9 illustrates a complementary version of the differential circuit shown in FIG. 8. The basic structure and operation of each of the level-shifting circuits 902a, 902b is identical to that of the level-shifting circuits 802a, 802b of FIG. 8, except for the presence and operation of additional level-shift capacitors C_LSAP, C_LSBP, switches 920a, 920b, and bias voltage nodes 923a, 923b. Like the circuit of FIG. 8, input nodes 916a, 916b in the circuit of FIG. 9 may, for example, be connected to respective outputs of a preceding amplifier stage. During each phase Φ₁, the switches 910a, 910b are opened so that level-shift capacitors C_LSAN, C_LSBN, C_LSAP, C_LSBP are disconnected from the positive and negative input nodes 916a, 916b, and the switches 912a, 912b, 914a, 914b, 920a, 920b are closed so that the plates of the level-shift capacitors C_LSAN C_LSBN, C_LSAP, C_LSBP are connected to reference voltage nodes 906a, 906b and bias voltage nodes 908a, 908b, 923a, 923b. The nodes 906a, 906b, 908a, 908b, 923a, 923b may, for example, be connected to outputs of one or more voltage sources that generate substantially constant voltages regardless of the loads attached thereto and the amount of charge transferred to or from the level-shift capacitors C_{LSAN CLSBN,} C_LSAP, C_LSBP. The nodes 906a, 906b, 908a, 908b, 923a, 923b may either be connected to separate voltage sources or to one or more shared voltage sources, depending on the layout and desired characteristics of the circuit. Connecting the level-shift capacitors C_LSAN C_LSBN, C_LSAP, C_LSBP across the nodes 906a, 906b, 908a, 908b, 923a, 923b thus sets the proper charges on the level-shift capacitors C_LSAN C_LSBN, C_LSAP, C_LSBP during the phase Φ₁. During each phase Φ₂, the switches 910a, 910b are closed and the switches 912a, 912b, 914a, 914b, 920a, 920b are opened, so that level-shift capacitors C_LSAN C_LSBN, C_LSAP, C_LSBP are connected back to the input nodes 916a, 916b, and act as batteries that force the correct bias voltages on the gates of NMOS transistors 918a, 918b and PMOS transistors 921a, 921b of the amplifier 904 for inputs that are equal to the reference voltages.

Accordingly, during each phase Φ₁, the charge on each of the level-shift capacitors C_LSAN C_LSBN, C_LSAP, C_LSBP can be completely restored to the intended value, and, if an error is introduced onto any of the level-shift capacitors C_LSAN C_LSBN, C_LSAP, C_LSBP during a phase Φ₂, it will be removed during the subsequent phase Φ₁ and will not affect the following phase Φ₂.

FIG. 10 shows an inventive level-shift circuit that embodies additional or different aspects of the invention. As shown, the circuit of FIG. 10 comprises first and second circuit stages 1001, 1003, with a level shifting circuit 1002 disposed therebetween. In the illustrated embodiment, the level shifting circuit 1002 comprises a capacitor C_LS and a switch 1014, with the capacitor being directly connected between an output of the first stage 1001 and the control electrode of an NMOS transistor 1018 included in the second stage 1003. As shown, the switch may be connected between a bias voltage node 1008 and the control electrode of NMOS transistor 1018.

In the example shown, the first stage 1001 comprises a single-ended amplifier 1007 and an associated switch 1005, and the second stage 1003 comprises a single-ended class A amplifier including an NMOS transistor 1018 and a current source load 1009. As shown, the switch 1005 may be connected between the input and the output of the amplifier 1007 and may be closed during each phase Φ₁ so as to cause the amplifier 1007 to autozero during those phases. As such, the output of the first stage 1001 functions as a reference voltage during each phase Φ₁. It should be appreciated that the first stage 1001 need not comprise an autozeroing amplifier, and may alternatively comprise any other preceding circuit stage that generates an output voltage equal to some “reference” value during each phase Φ₁.

In the example shown, during each phase Φ₁, the switches 1005, 1014 are closed so that the respective plates of the level-shift capacitor C_LS are connected to the zeroed output of the amplifier stage 1001 and a bias voltage node 1008. The node 1008 may, for example, be connected to an output of a voltage source that generates a substantially constant voltage regardless of the load attached thereto and the amount of charge transferred to or from the level-shift capacitor C_LS. Connecting the level-shift capacitor C_LS across these nodes thus sets the proper charge on the level-shift capacitor C_LS during the phase Φ₁. During each phase Φ₂, the switches 1005, 1014 are opened, thus taking the amplifier 1007 out of its autozeroed state, but leaving the fully-charged level-shift capacitor C_LS connected between the output of the amplifier 1007 and the control electrode of the NMOS transistor 1018. The level-shift capacitor C_LS thus acts as a battery that forces the correct bias voltage on the gate of the NMOS transistor 1018 during each phase Φ₂.

The circuit of FIG. 10 does not have the slow recovery problem discussed above in connection with FIG. 5, because during each phase Φ₁, the charge on the level-shift capacitor C_LS can be completely restored to the intended value. Therefore, if an error is introduced onto the level-shift capacitor C_LS during a phase Φ₂, it will be removed during the subsequent phase Φ₁ and will not affect the following phase Φ₂.

FIG. 11 shows a differential version of the circuit of FIG. 10. Like the circuit of FIG. 10, the circuit of FIG. 11 comprises first and second circuit stages 1101, 1103, with a level shifting circuit 1102 disposed therebetween. As shown, in the differential embodiment, one half 1102a of the level shifting circuit 1102 comprises a capacitor C_LSA and a switch 1114a, and the other half 1102b of the level shifting circuit 1102 comprises a capacitor C_LSB and a switch 1114b. The capacitors C_LSA, C_LSB are directly connected between respective differential outputs of the first stage 1101 and the control electrodes of NMOS transistor 1118a, 1118b included in the second stage 1103. The switches are connected between bias voltage nodes 1108a, 1108b and the control electrodes of the NMOS transistors 1118a, 1118b.

As shown, the first stage 1101 may comprise a differential amplifier 1107 and associated switches 1105a, 1105b, and the second stage 1103 may comprise a differential class A amplifier including the NMOS transistors 1118a, 1118b and current source loads 1109a, 1109b. In the example shown, the switches 1105a, 1105b are connected between the respective differential inputs and outputs of the amplifier 1107 and are closed during each phase Φ₁ so as to cause the amplifier 1107 to autozero during that phase. As such, the outputs of the first stage 1101 function as a reference voltage during each phase Φ₁. It should be appreciated that the first stage 1101 need not comprise an autozeroing amplifier, and may alternatively comprise any other preceding circuit stage that generates an output voltage equal to some “reference” value during each phase Φ₁.

In the example shown, during each phase Φ₁, the switches 1105a, 1105b, 1114a, 1114b are closed so that the respective plates of level-shift capacitors C_LSA, C_LSB are connected to the zeroed outputs of the amplifier 1107 and bias voltage nodes 1108a, 1108b. The nodes 1108a, 1108b may, for example, be connected to outputs of one or more voltage sources that generate substantially constant voltages regardless of the load attached thereto and the amount of charge transferred to or from the level-shift capacitor C_LSA, C_LSB. Connecting the level-shift capacitors C_LSA, C_LSB across these nodes thus sets the proper charges on the level-shift capacitors C_LSA, C_LSB during the phase Φ₁. During each phase Φ₂, the switches 1105a, 1105b, 1114a, 1114b are opened, thus taking the amplifier 1107 out of its autozeroed state, but leaving the fully-charged level-shift capacitors C_LSA, C_LSB connected between the differential outputs of the amplifier 1107 and the control electrodes of the NMOS transistors 1118a, 1118b. The level-shift capacitors C_LSA, C_LSB thus act as batteries that force the correct bias voltages on the gates of the NMOS transistors 1118a, 1118b during each phase Φ₂.

Thus, during each phase Φ₁, the charges on the level-shift capacitors C_LSA, C_LSB can be completely restored to the intended values. Therefore, if any errors are introduced onto the level-shift capacitors C_LSA, C_LSB during a phase Φ₂, they will be removed during the subsequent phase Φ₁ and will not affect the following phase Φ₂.

FIG. 12 shows a complementary version of the differential circuit of FIG. 11. Like the circuits of FIGS. 10 and 11, the circuit of FIG. 12 comprises first and second circuit stages 1101, 1103, with a level shifting circuit 1102 disposed therebetween. As shown, in the embodiment of FIG. 12, one half 1202a of the level shifting circuit 1202 comprises a pair of capacitors C_LSAN, C_LSAP and a corresponding pair of switches 1214a, 1220a, and the other half 1202b of the level shifting circuit 1202 comprises a pair of capacitors C_LSBN, C_LSBP and a corresponding pair of switches 1214b, 1220b. As shown, in this embodiment, the capacitors C_LSAN, C_LSBN, C_LSAP, C_LSBP are directly connected between differential outputs of the first stage 1201 and the control electrodes of respective ones of NMOS transistor 1218a, 1218b and PMOS transistors 1221a, 1221b included in the second stage 1203. The switches 1214a, 1214b, 1220a, 1220b are connected between bias voltage nodes 1208a, 1208b, 1223a, 1223b and the control electrodes of the NMOS transistors 1218a, 1218b, and PMOS transistors 1221a, 1221b.

As shown, the first stage 1201 may comprise a differential amplifier 1207 and associated switches 1205a, 1205b, and the second stage may comprise a differential class AB amplifier including the NMOS transistors 1218a, 1218b and the PMOS transistors 1221a, 1221b. In the example shown, the switches 1205a, 1205b are connected between the respective differential inputs and outputs of the amplifier 1207 and are closed during each phase Φ₁ so as to cause the amplifier 1207 to autozero during that phase. As such, the outputs of the first stage 1201 function as a reference voltage during each phase Φ₁. It should be appreciated that the first stage 1201 need not comprise an autozeroing amplifier, and may alternatively comprise any other preceding circuit stage that generates an output voltage equal to some “reference” value during each phase Φ₁.

In the example shown, during each phase Φ₁, the switches 1205a, 1205b, 1214a, 1214b, 1220a, 1220b are closed so that the respective plates of level-shift capacitors C_LSAN, C_LSBN, C_LSAP, C_LSBP are connected to the zeroed outputs of the amplifier 1207 and bias voltage nodes 1208a, 1208b, 1223a, 1223b. The nodes 1208a, 1208b, 1223a, 1223b may, for example, be connected to outputs of one or more voltage sources that generate substantially constant voltages regardless of the load attached thereto and the amount of charge transferred to or from the level-shift capacitors C_LSAN, C_LSBN, C_LSAP, C_LSBP. Connecting the level-shift capacitors C_LSAN, C_LSBN, C_LSAP, C_LSBP across these nodes thus sets the proper charges on the level-shift capacitors C_LSAN, C_LSBN, C_LSAP, C_LSBP during the phase Φ₁. During each phase Φ₂, the switches 1205a, 1205b, 1214a, 1214b, 1220a, 1220b are opened, thus taking the amplifier 1207 out of its autozeroed state, but leaving the fully-charged level-shift capacitors C_LSAN, C_LSBN, C_LSAP, C_LSBP connected between the differential outputs of the amplifier 1207 and the control electrodes of the NMOS transistors 1218a, 1218b and the PMOS transistors 1221a, 1221b. The level-shift capacitors C_LSAN, C_LSBN, C_LSAP, C_LSBP thus act as batteries that force the correct bias voltages on the gates of the NMOS transistors 1218a, 1218b and the PMOS transistors 1221a, 1221b during each phase Φ₂.

Thus, during each phase Φ₁, the charges on the level-shift capacitors C_LSAN, C_LSBN, C_LSAP, C_LSBP can be completely restored to the intended values. Therefore, if any errors are introduced onto the level-shift capacitors C_LSAN, C_LSBN, C_LSAP, C_LSBP during a phase Φ₂, they will be removed during the subsequent phase Φ₁ and will not affect the following phase Φ₂.

Another example of an inventive level-shifting circuit for use in level shifting the input of an amplifier or otherwise is shown in FIG. 13. In the example shown, level-shifting circuit 1302 comprises two halves 1302a, 1302b that are configured and arranged to level shift the input voltages of a differential class A common-source amplifier 1304. Like the other circuits discussed above, input nodes 1316a, 1316b in the circuit of FIG. 13 may, for example, be connected to respective outputs of a preceding amplifier stage. As shown, the half 1302a of the level-shifting circuit 1302 comprises two level-shift capacitors C_LS1A and C_LS2A, and eight switches 1322a, 1324a, 1326a, 1328a, 1330a, 1332a, 1334a, 1336a, and the half 1302b of the level-shifting circuit 1302 comprises two level-shift capacitors C_LS1B and C_LS2B, and eight switches 1322b, 1324b, 1326b, 1228b, 1330b, 1332b, 1334b, 1336b.

During each phase Φ₁, eight of the switches 1322a, 1324a, 1326a, 1328a, 1322b, 1324b, 1326b, 1328b are closed, and the other eight switches 1330a, 1332a, 1334a, 1336a, 1330b, 1332b, 1334b, 1336b are opened, thus causing two of the level-shift capacitors C_LS2A, C_LS2B to be connected between reference voltage nodes 1306a, 1306b and bias voltage nodes 1308a, 1308b and to be disconnected from the input nodes 1316a, 1316b and the gates of the transistors 1318a, 1318b of the amplifier 1304, while the other two level-shift capacitors C_LS1A, C_LS1B are connected between the input nodes 1316a, 1316b and the gates of the transistors 1318a, 1318b of the amplifier 1304 and are disconnected from the reference voltage nodes 1306a, 1306b and the bias voltage nodes 1308a, 1308b.

During each phase Φ₂, the eight switches 1330a, 1332a, 1334a, 1336a, 1330b, 1332b, 1334b, 1336b are closed, and the eight switches 1322a, 1324a, 1326a, 1328a, 1322b, 1324b, 1326b, 1328b are opened, thus causing the level-shift capacitors C_LS1A, C_LS1B to be connected between the reference voltage nodes 1306a, 1306b and the bias voltage nodes 1308a, 1308b and to be disconnected from the input nodes 1316a, 1316b and the gates of the transistors 1318a, 1318b of the amplifier 1304, while the level-shift capacitors C_LS2A, C_LS2B are connected between the input nodes 1316a, 1316b and the gates of the transistors 1318a, 1318b of the amplifier 1304 and are disconnected from the reference voltage nodes 1306a, 1306b and the bias voltage nodes 1308a, 1308b.

The nodes 1306a, 1306b, 1308a, 1308b may, for example, be connected to outputs of one or more voltage sources that generate substantially constant voltages regardless of the load attached thereto and the amount of charge transferred to or from the level-shift capacitors C_LS1A, C_LS2A, C_LS1B, C_LS2B. Connecting the level-shift capacitors C_LS1A, C_LS2A, C_LS1B, C_LS2B across the nodes 1306a, 1306b, 1308a, 1308b thus sets the proper charge on the level-shift capacitors C_LS1A, C_LS2A, C_LS1B, C_LS2B during respective phases Φ₁, Φ₂. The nodes 1306a, 1306b, 1308a, 1308b may either be connected to separate voltage sources or to a shared voltage source, depending on the layout and desired characteristics of the circuit.

The capacitors C_LS1A and C_LS2A, as well as the capacitors C_LS1B and C_LS2B, are thus swapped with one another at the beginning of each of the phases Φ₁ and Φ₂, with two of them being charged and the other two actively introducing voltage level shifts to the amplifier input nodes during each phase. As such, any error charges introduced during one phase will be removed from the capacitors during the next phase. Also, in this configuration there are always capacitors connected between the input nodes 1316a, 1316b and the gates of the transistors 1318a, 1318b of the amplifier 1304, thus allowing the level-shift to operate during both phases.

FIG. 14 shows a complementary version of the circuit of FIG. 13. In the example shown, level-shifting circuit 1402 comprises two halves 1402a, 1402b that are configured and arranged to level shift the input voltages of a differential class AB common-source amplifier 1404. Like the other circuits discussed above, input nodes 1416a, 1416b in the circuit of FIG. 14 may, for example, be connected to respective outputs of a preceding amplifier stage. As shown, the half 1402a of the level-shifting circuit 1402 comprises four level-shift capacitors C_LS1A, C_LS2A, C_LS3A, C_LS4A and sixteen switches 1422a, 1424a, 1426a, 1428a, 1430a, 1432a, 1434a, 1436a, 1438a, 1440a, 1442a, 1444a, 1446a, 1448a, 1450a, 1452a, and the half 1402b of the level-shifting circuit 1402 comprises four level-shift capacitors C_LS1B, C_LS2B, C_LS3B, C_LS4B and sixteen switches 1422b, 1424b, 1426b, 1428b, 1430b, 1432b, 1434b, 1436b, 1438b, 1440b, 1442b, 1444b, 1446b, 1448b, 1450b, 1452b.

During each phase Φ₁, sixteen of the switches 1422a, 1424a, 1426a, 1428a, 1422b, 1424b, 1426b, 1428b, 1438a, 1440a, 1442a, 1444a, 1438b, 1440b, 1442b, 1444b are closed, and the other sixteen switches 1430a, 1432a, 1434a, 1436a, 1430b, 1432b, 1434b, 1436b, 1446a, 1448a, 1450a, 1452a, 1446b, 1448b, 1450b, 1452b are opened, thus causing four of the level-shift capacitors C_LS2A, C_LS2B, C_LS4A, C_LS4B to be connected between reference voltage nodes 1406a, 1406b and bias voltage nodes 1408a, 1408b, 1423a, 1423b and to be disconnected from the input nodes 1416a, 1416b and the gates of the transistors 1418a, 1418b, 1421a, 1421b of the amplifier 1404, while the other four level-shift capacitors C_LS1A, C_LS1B, C_LS3A, C_LS3B are connected between the input nodes 1416a, 1416b and the gates of the transistors 1418a, 1418b, 1421a, 1421b of the amplifier 1404 and are disconnected from the reference voltage nodes 1406a, 1406b and the bias voltage nodes 1408a, 1408b, 1423a, 1423b.

During each phase Φ₂, the sixteen switches 1430a, 1432a, 1434a, 1436a, 1430b, 1432b, 1434b, 1436b, 1446a, 1448a, 1450a, 1452a, 1446b, 1448b, 1450b, 1452b are closed, and the sixteen switches 1422a, 1424a, 1426a, 1428a, 1422b, 1424b, 1426b, 1428b, 1438a, 1440a, 1442a, 1444a, 1438b, 1440b, 1442b, 1444b are opened, thus causing the level-shift capacitors C_LS1A, C_LS1B, C_LS3A, C_LS3B to be connected between the reference voltage nodes 1406a, 1406b and the bias voltage nodes 1408a, 1408b, 1423a, 1423b and to be disconnected from the input nodes 1416a, 1416b and the gates of the transistors 1418a, 1418b, 1421a, 1421b of the amplifier 1404, while the level-shift capacitors C_LS2A, C_LS2B, C_LS4A, C_LS4B are connected between the input nodes 1416a, 1416b and the gates of the transistors 1418a, 1418b, 1421a, 1421b of the amplifier 1404 and are disconnected from the reference voltage nodes 1406a, 1406b and the bias voltage nodes 1408a, 1408b, 1423a, 1423b.

The nodes 1406a, 1406b, 1408a, 1408b, 1423a, 1423b may, for example, be connected to outputs of one or more voltage sources that generate substantially constant voltages regardless of the load attached thereto and the amount of charge transferred to or from the level-shift capacitors C_LS1A, C_LS1B, C_LS2A, C_LS2B, C_LS3A, C_LS3B, C_LS4A, C_LS4B. Connecting the level-shift capacitors C_LS1A, C_LS1B, C_LS2A, C_LS2B, C_LS3A, C_LS3B, C_LS4A, C_LS4B across the nodes 1406a, 1406b, 1408a, 1408b, 1423a, 1423b thus sets the proper charge on the level-shift capacitors C_LS1A, C_LS1B, C_LS2A, C_LS2B, C_LS3A, C_LS3B, C_LS4A, C_LS4B during respective phases Φ₁, Φ₂. The nodes 1406a, 1406b, 1408a, 1408b, 1423a, 1423b may either be connected to separate voltage sources or to one or more shared voltage source, depending on the layout and desired characteristics of the circuit.

The two capacitors included in each pair of capacitors C_LS1A and C_LS2A, C_LS1B and C_LS2B, C_LS1C and C_LS2C, C_LS1D and C_LS2D, are thus swapped with one another at the beginning of each of the phases Φ₁ and Φ₂, such that one group of four capacitors is being charged and another group of four capacitors is actively introducing voltage level shifts to the amplifier input nodes during each phase. As such, any error charges introduced during one phase will be removed from the capacitors during the next phase. Also, in this configuration there are always capacitors connected between the input nodes 1416a, 1416b and the gates of the transistors 1418a, 1418b, 1421a, 1421b of the amplifier 1404, thus allowing the level-shift to operate during both phases.

In alternative embodiments of the circuits shown in FIGS. 13 and 14, one or more additional capacitors and associated switches can be employed in the level-shifting circuit corresponding to each amplifier input node. An illustrative example of such a level-shifting circuit, which employs four, rather than two, level-shift capacitors C_LS1, C_LS2, C_LS3, C_LS4, to accomplish the level-shifting for an input node 1554 of a succeeding circuit, e.g., a gate of an input transistor of an amplifier, is shown in FIG. 15. In operation, switches 1556-1588 may be controlled so that each of the level-shift capacitors C_LS1, C_LS2, C_LS3, C_LS4 is connected between the input node 1516 and the input node of the succeeding circuit 1554 during a respective one of four phases Φ₁, Φ₂, Φ₃, Φ₄, and is connected between a reference voltage node 1506 and a bias voltage node 1508 during one or more (and preferably all) of the phases Φ₁, Φ₂, Φ₃, Φ₄ during which it is not connected between the input node 1516 and the input of the succeeding circuit 1554.

FIG. 16 illustrates clock signals that may be generated to control the switches in an embodiment such as that shown in FIG. 15 wherein all of the switches are configured to be closed in response to a logical high state. It should be appreciated, however, that any of numerous clocking schemes and switch types could be employed to perform such a function, and the invention is not limited in this respect. As shown, the clock signal 1602 may be used to control the switches 1556, 1558, the clock signal 1604 may be used to control the switches 1560, 1562, the clock signal 1606 may be used to control the switches 1564, 1566, the clock signal 1608 may be used to control the switches 1568, 1570, the clock signal 1610 may be used to control the switches 1572, 1574, the clock signal 1612 may be used to control the switches 1576, 1578, the clock signal 1614 may be used to control the switches 1580, 1582, and the clock signal 1616 may be used to control the switches 1584, 1586.

Though shown with particular amplifier topologies, any of the level-shifting circuits disclosed herein can be used as the level-shift in various other amplifier topologies, or in any other application in which a level shift may be desirable or required. For instance, although not explicitly shown, it should be appreciated that, in some embodiments, one-half of any of the differential circuits of FIGS. 9, 12, and 14, i.e., a level-shifted single-ended class AB topology, may alternatively be employed. Also, although most of the examples presented herein are of common-source topologies, the invention is not limited in that respect, as common-drain topologies can likewise be employed. Moreover, although the examples presented herein employ metal oxide semiconductor field effect transistors (MOSFET), the disclosed level-shifting circuits and techniques may likewise be employed in layouts employing bipolar junction transistors (BJTs) or any other type of transistors or other devices.

Having described several embodiments of the invention in detail, various modifications and improvements will readily occur to those skilled in the art. Such modifications and improvements are intended to be within the spirit and scope of the invention. Accordingly, the foregoing description is by way of example only, and is not intended as limiting. The invention is limited only as defined by the following claims and the equivalents thereto.

Claims

1. A method, comprising steps of:

(a) providing a circuit comprising at least first and second circuit stages and a first level-shift capacitor, each of the first and second circuit stages comprising at least one input, at least one output, and at least one signal processing element coupled therebetween;

(b) receiving at least one signal that defines at least first and second phases;

(c) providing a first circuit node having a first approximately constant voltage thereon at least during the first and second phases, wherein the first approximately constant voltage remains approximately constant when a significant amount of charge is transferred between the first circuit node and the first level shift capacitor during a first phase;

(d) providing a second circuit node having a first reference voltage thereon at least during the first phases;

(e) during each first phase, configuring the circuit such that respective plates of the first level-shift capacitor are connected to the first and second circuit nodes, thereby allowing the first level-shift capacitor to charge to a level-shift voltage equal to a difference between the first approximately constant voltage and the first reference voltage; and

(f) during each second phase, configuring the circuit such that the respective plates of the first level-shift capacitor are connected to a first output of the first circuit stage and a first input of the second circuit stage, without causing the first level-shift capacitor to be connected in parallel with another capacitor with which it was not connected in parallel during a preceding first phase, thereby introducing the voltage across the first level-shift capacitor as an offset voltage between the first and second circuit stages.

2. The method of claim 1, wherein the first and second circuit stages comprise first and second amplifier stages of an amplifier circuit.

3. The method of claim 1, further comprising steps of:

(g) providing a second level shift capacitor;

(h) providing a third circuit node having a second approximately constant voltage thereon at least during the first and second phases, wherein the second approximately constant voltage remains approximately constant when a significant amount of charge is transferred between the third circuit node and the second level shift capacitor during a first phase;

(i) providing a fourth circuit node having a second reference voltage thereon at least during the first phases;

(j) during each first phase, configuring the circuit such that respective plates of the second level-shift capacitor are connected to the third and fourth circuit nodes, thereby allowing the second level-shift capacitor to charge to a level-shift voltage equal to a difference between the second approximately constant voltage and the second reference voltage; and

(k) during each second phase, configuring the circuit such that the respective plates of the second level-shift capacitor are connected to a second output of the first circuit stage and a second input of the second circuit stage, without causing the second level-shift capacitor to be connected in parallel with another capacitor with which it was not connected in parallel during a preceding first phase, thereby introducing the voltage across the second level-shift capacitor as an offset voltage between the first and second circuit stages.

4. The method of claim 3, wherein the first and second circuit stages comprise first and second amplifier stages of an amplifier circuit, and wherein the first and second inputs of the second amplifier stage comprise respective inputs of a differential amplifier stage.

5. The method of claim 2, wherein:

the step (e) comprises configuring the circuit such that neither plate of the first level- shift capacitor is connected to the first output of the first amplifier stage during each first phase.

6. The method of claim 2, wherein the second circuit node corresponds to the first output of the first amplifier stage, and the method further comprises steps of:

(g) causing the first amplifier stage to produce an approximately constant reference voltage at the first output thereof during each first phase; and

(h) allowing the first amplifier stage to produce a variable voltage at the first output thereof during each second phase.

7. The method of claim 6, wherein:

the step (g) comprises controlling at least one switch so as to cause an input of the first amplifier stage to be connected to the first output of the first amplifier stage during each first phase; and

the step (h) comprises controlling the at least one switch so as to cause the input of the first amplifier stage to be disconnected from the first output of the first amplifier stage during each second phase.

8. The method of claim 1, further comprising steps of:

(g) providing a second level shift capacitor;

(h) during each first phase, configuring the circuit such that respective plates of the second level-shift capacitor are connected to the first output of the first circuit stage and the first input of the second circuit stage, without causing the second level-shift capacitor to be connected in parallel with another capacitor with which it was not connected in parallel during a preceding second phase, thereby introducing the voltage across the second level-shift capacitor as an offset voltage between the first and second circuit stages; and

(i) during each second phase, configuring the circuit such that the respective plates of the second level-shift capacitor are connected to the first and second circuit nodes, thereby allowing the second level-shift capacitor to charge to a level-shift voltage equal to a difference between the first approximately constant voltage and the first reference voltage.

9. A method, comprising steps of:

(a) providing a circuit comprising at least first and second circuit stages and a first level-shift capacitor, wherein each of the first and second circuit stages comprises at least one input, at least one output, and at least one signal processing element coupled therebetween, and wherein the at least one output of the second circuit stage is connected to a load;

(b) receiving at least one signal that defines at least first and second phases;

(c) providing a first circuit node having a first approximately constant voltage thereon at least during the first phases, wherein the first approximately constant voltage remains approximately constant when a significant amount of charge is transferred between the first circuit node and the first level-shift capacitor during a first phase, and wherein the at least one output of the second circuit stage remains connected to the load when the first approximately constant voltage is established on the first node during the first phases;

(d) providing a second circuit node having a first reference voltage thereon at least during the first phases;

(e) during each first phase, configuring the circuit such that respective plates of the first level-shift capacitor are connected to the first and second circuit nodes, thereby allowing the first level-shift capacitor to charge to a level-shift voltage equal to a voltage difference between the first approximately constant voltage and the first reference voltage; and

(f) during each second phase, configuring the circuit such that the respective plates of the first level-shift capacitor are connected to a first output of the first circuit stage and a first input of the second circuit stage, without causing the first level-shift capacitor to be connected in parallel with another capacitor with which it was not connected in parallel during a preceding first phase, thereby introducing the voltage across the first level-shift capacitor as an offset voltage between the first and second circuit stages.

10. The method of claim 9, wherein the first and second circuit stages comprise first and second amplifier stages of an amplifier circuit.

11. The method of claim 9, further comprising steps of:

(g) providing a second level shift capacitor;

(h) providing a third circuit node having a second approximately constant voltage thereon at least during the first phases, wherein the second approximately constant voltage remains approximately constant when a significant amount of charge is transferred between the third circuit node and the second level-shift capacitor during a first phase, and wherein the at least one output of the second circuit stage remains connected to the load when the first approximately constant voltage is established on the third node during the first phases;

(i) providing a fourth circuit node having a second reference voltage thereon at least during the first phases;

(j) during each first phase, configuring the circuit such that respective plates of the second level-shift capacitor are connected to the third and fourth circuit nodes, thereby allowing the second level-shift capacitor to charge to a level-shift voltage equal to a difference between the second approximately constant voltage and the second reference voltage; and

(k) during each second phase, configuring the circuit such that the respective plates of the second level-shift capacitor are connected to a second output of the first circuit stage and a second input of the second circuit stage, without causing the second level-shift capacitor to be connected in parallel with another capacitor with which it was not connected in parallel during a preceding first phase, thereby introducing the voltage across the second level-shift capacitor as an offset voltage between the first and second circuit stages.

12. The method of claim 11, wherein the first and second circuit stages comprise first and second amplifier stages of an amplifier circuit, and wherein the first and second inputs of the second amplifier stage comprise respective inputs of a differential amplifier stage.

13. The method of claim 9, further comprising steps of:

(g) providing a second level shift capacitor;

(h) during each first phase, configuring the circuit such that the respective plates of the second level-shift capacitor are connected to the first output of the first circuit stage and the first input of the second circuit stage, without causing the second level-shift capacitor to be connected in parallel with another capacitor with which it was not connected in parallel during a preceding first phase, thereby introducing the voltage across the second level-shift capacitor as an offset voltage between the first and second circuit stages; and

(i) during each second phase, configuring the circuit such that the respective plates of the second level-shift capacitor are connected to the first and second circuit nodes, thereby allowing the second level-shift capacitor to charge to a level-shift voltage equal to a difference between the first approximately constant voltage and the first reference voltage.

14. A circuit, comprising:

a first circuit stage comprising at least one first input, at least one first output, and at least one first signal processing element coupled therebetween, the first circuit stage being configured and arranged to produce a reference voltage at the at least one first output during each first phase of at least first and second phases, and to produce an output signal at the at least one first output that is responsive to an input signal at the at least one first input during each second phase of the at least first and second phases;

a second circuit stage comprising at least one second input, at least one second output, and at least one second signal processing element coupled therebetween;

at least one level shifting circuit, comprising at least one capacitor and at least one switch, coupled between the first circuit stage and the second circuit stage; and

a control circuit configured to control the level shifting circuit such that, during each first phase, respective plates of the at least one capacitor are connected to the at least one first output of the first circuit stage and a source of an approximately constant voltage so as to allow the at least one capacitor to be charged to a level-shift voltage equal to a difference between the approximately constant voltage and the reference voltage, and such that, during each second phase, the respective plates of the at least one capacitor are connected to the at least one first output and the at least one second input to thereby introduce the level-shift voltage across the at least one capacitor as an offset voltage therebetween.

15. The circuit of claim 14, wherein the source of the approximately constant voltage is configured and arranged such that the approximately constant voltage remains approximately constant when a significant amount of charge is transferred between the source of the approximately constant voltage and the at least one capacitor during a first phase.

16. The circuit of claim 14, wherein:

the first and second circuit stages comprise respective amplifier stages of a multi-stage amplifier;

the first circuit stage further comprises at least one autozeroing switch connected between an input and an output of the first stage; and

the first circuit stage is configured and arranged such that the at least one autozeroing switch is closed during each first phase and opened during each second phase.

17. A method, comprising steps of:

(a) providing a circuit comprising first and second circuit stages, and first, second, third, and fourth level-shifting capacitors, wherein each of the first and second circuit stages comprises at least one input, at least one output, and at least one signal processing element coupled therebetween, and wherein the second circuit stage comprises first and second differential inputs;

(b) receiving at least one signal that defines at least first and second phases;

(c) providing first and second circuit nodes having approximately constant voltages thereon at least during the first phases, and third and fourth circuit nodes having reference voltages thereon at least during the first phases;

(d) during each first phase, configuring the circuit such that (1) respective plates of the first level-shift capacitor are connected to the first and third circuit nodes, (2) respective plates of the second level-shift capacitor are connected to the second and fourth voltage nodes, (3) respective plates of the third level-shift capacitor are connected to an output of the first circuit stage and the first differential input of the second circuit stage, and (4) respective plates of the fourth level-shift capacitors are connected to an output of the first circuit stage and the second differential input of the second circuit stage; and

(e) during each second phase, configuring the circuit such that (1) respective plates of the third level-shift capacitor are connected to the first and third circuit nodes, (2) respective plates of the fourth level-shift capacitor are connected to the second and fourth voltage nodes, (3) respective plates of the first level-shift capacitor are connected to an output of the first circuit stage and the first differential input of the second circuit stage, and (4) respective plates of the second level-shift capacitors are connected to an output of the first circuit stage and the second differential input of the second circuit stage.

18. The method of claim 17, wherein the first and second circuit stages comprise first and second amplifier stages of an amplifier circuit.

19. The method of claim 17, wherein:

the step (d) comprises configuring the circuit during each first phase such that neither plate of either of the first and second level-shift capacitors is connected to an output of the first circuit stage; and

the step (e) comprises configuring the circuit during each second phase such that neither plate of either of the third and fourth level-shift capacitors is connected to an output of the first circuit stage.

20. The method of claim 17, wherein the first circuit stage comprises a differential amplifier stage having first and second differential outputs, and wherein:

the step (d) comprises configuring the circuit during each first phase such that the respective plates of the third level-shift capacitor are connected to the first differential output of the first amplifier stage and the first differential input of the second circuit stage, and the respective plates of the fourth level-shift capacitor are connected to the second differential output of the first amplifier stage and the second differential input of the second circuit stage; and

the step (e) comprises configuring the circuit during each second phase such that the respective plates of the first level-shift capacitor are connected to the first differential output of the first amplifier stage and the first differential input of the second circuit stage, and the respective plates of the second level-shift capacitor are connected to the second differential output of the first amplifier stage and the second differential input of the second circuit stage.