A synchronous rectifying circuit for a flyback converter includes a synchronous rectifying element (Q2) coupled to the secondary winding (N2) of a transformer (T) and performing a synchronous rectifying operation according to an on/off operation of the synchronous rectifying element; an auxiliary inductance circuit (L3) coupled to the secondary winding (N2) of the transformer (T) and having an energy discharge time period shorter than that of the secondary winding (N2); and a control element (Q3) for turning the synchronous rectifying element (Q2) off in response to the detection of termination of the energy discharge of the auxiliary inductance circuit (L3).
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1. A synchronous rectifying circuit for a flyback converter, comprising:
a transformer having a primary winding and a secondary winding; a synchronous rectifying element coupled to the secondary winding of the transformer and performs a synchronous rectifying operation by turning on and off; an auxiliary inductance circuit coupled to the secondary winding of the transformer and has shorter energy discharge time period in comparison with the secondary winding; and a control element for turning off the synchronous rectifying element when a termination of energy discharge of the auxiliary inductance circuit is detected.
2. The synchronous rectifying circuit as claimed in
the synchronous rectifying element comprises a field effect transistor; and the control element turns off the synchronous rectifying element by discharging electric charges accumulated in a gate of the field effect transistor.
3. The synchronous rectifying circuit as claimed in
the transformer has an auxiliary winding extending from the secondary winding, further comprising: an isolation diode element coupled between the auxiliary winding and the auxiliary inductance circuit. 4. The synchronous rectifying circuit as claimed in
a control element coupled to the auxiliary winding and turns on the synchronous rectifying element.
5. The synchronous rectifying circuit as claimed in
a control element coupled to the secondary winding and turns on the synchronous rectifying element.
6. The synchronous rectifying circuit as claimed in
the transformer has an auxiliary winding extending from the secondary winding, further comprising: an isolation diode element coupled between the auxiliary winding and the auxiliary inductance circuit. 7. The synchronous rectifying circuit as claimed in
a control element coupled to the auxiliary winding and turns on the synchronous rectifying element.
8. The synchronous rectifying circuit as claimed in
a control element coupled to the secondary winding and turns on the synchronous rectifying element.
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The present disclosure relates to the subject matter contained in Japanese Patent Application No. 2002-094276 filed on Mar. 29, 2002, which is incorporated herein by reference in its entirety.
1. Field of the Invention
The present invention relates to a synchronous rectifying circuit, which is a kind of switching regulators, for a flyback converter.
2. Description of the Related Art
Conventionally, in a switching regulator, a synchronous rectifying circuit is known as a rectifying circuit for attaining a high efficiency. On one hand, a self-excited type flyback converter, often referred to as the ringing choke converter (RCC), which is a kind of switching regulators is most cheap among the switching regulators of about 50 watt or less, and so employed widely in an AC adapter etc. The synchronous rectifying circuit has been tried to be applied to such a self-excited type flyback converter in various manners, but sufficient effects have not been obtained. The reason why it is difficult to apply the synchronous rectifying circuit to the self-excited type flyback converter is that it is difficult to detect the turn-off timing of a rectifying diode in addition to that the switching frequency changes largely depending on amount of a load to be coupled.
In particular, in the ZVS (zero volt switching) utilizing the resonance with the leakage inductance of a transformer which has been performed recently in the switching of the primary side, the slope of reduction of a voltage from the time point near the turning-off of a rectifying diode is gentle, so that it has been increasingly difficult to apply the synchronous rectifying circuit.
Also, when a synchronous rectifying transistor is turned on at the time of turning the rectifying diode off, a large reverse pulse current flows. Thus, not only efficiency is degraded but also the synchronous rectifying transistor is broken at the worst.
In the meantime, various kinds of synchronous rectifying circuits each using a current transformer has been proposed. Examples are disclosed in U.S. Pat. No. 3,066,727 and JP-A-2002-10639.
The synchronous rectifying circuit of the current transformer type is configured to control the switching operation of a synchronous rectifying transistor by a voltage generated at a secondary winding in accordance with an output current flowing through the primary winding of the current transformer.
However, the aforesaid conventional synchronous rectifying circuit has the following drawbacks. (1) Considerable amount of a consumption of electric power by the current transformer. (2) The high price of the current transformer itself. (3) Large amount of the switching loss caused by the slow switching speed to an off state due to the gate input capacitance of the synchronous rectifying transistor, and by the moderate curvature of the increase/decrease rate of a voltage generated at the secondary winding of the current transformer. (4) Incapability of a wide range load due to the inability to switch the synchronous rectifying transistor when the load is small and the voltage level itself generated at the secondary winding of the current transformer becomes low.
The invention was made in view of such a conventional circumference and an object of the invention is to provide a synchronous rectifying circuit for a flyback converter which can eliminate the drawbacks of the current transformer type, that is, a synchronous rectifying circuit for a flyback converter which is high in efficiency, cheap and can cope with a wide range load.
In order to achieve the above object, according to a first aspect of the invention, there is provided a synchronous rectifying circuit for a flyback converter, including: a transformer having a primary winding and a secondary winding; a synchronous rectifying element coupled to the secondary winding of the transformer and performs a synchronous rectifying operation by turning on and off; an auxiliary inductance circuit coupled to the secondary winding of the transformer and has shorter energy discharge time period in comparison with the secondary winding; and a control element for turning off the synchronous rectifying element when a termination of energy discharge of the auxiliary inductance circuit is detected.
According to the synchronous rectifying circuit for a flyback converter thus configured, the circuit can be configured so as to be small in the voltage loss and also low in the cost (almost {fraction (1/10)} of the cost of the synchronous rectifying circuit using the current transformer). Further, since the auxiliary inductance circuit shorter in the energy discharge time period than that of the secondary winding of the transformer is employed and the termination of the energy discharge of the auxiliary inductance circuit is detected by the control element thereby to turn the synchronous rectifying element off, the switching loss can be made small.
According to a second aspect of the invention, in arrangement of the synchronous rectifying circuit in the aforesaid first aspect, the synchronous rectifying element includes a field effect transistor; and the control element turns off the synchronous rectifying element by discharging electric charges accumulated in a gate of the field effect transistor.
In this configuration, since the termination of the energy discharge of the auxiliary inductance circuit is detected by the control element thereby to discharge the electric charges accumulated in the gate of the field effect transistor and turn the field effect transistor off, the switching loss can be made small.
According to a third aspect of the invention, in arrangement of the synchronous rectifying circuit in the aforesaid first or second aspect, the transformer has an auxiliary winding extending from the second winding, and further including an isolation diode element coupled between the auxiliary winding and the auxiliary inductance circuit.
In this configuration, at the time of turning-on of the synchronous rectifying element by the auxiliary inductance circuit, reminder of the energy is regenerated to the auxiliary winding through the isolation diode element.
According to a fourth aspect of the invention, in arrangement of the synchronous rectifying circuit in the aforesaid third aspect, may further include a control element coupled to the auxiliary winding and turns on the synchronous rectifying element.
In this configuration, the synchronous rectifying element is turned on by the control element coupled to the auxiliary winding.
According to a fifth aspect of the invention, in arrangement of the synchronous rectifying circuit in the aforesaid first or second aspect, may further include a control element coupled to the secondary winding and turns on the synchronous rectifying element.
In this configuration, the synchronous rectifying element is turned on by the control element coupled to the secondary winding.
The above objects and advantages of the present invention will become more apparent by describing in detail preferred exemplary embodiments thereof with reference to the accompanying drawings, wherein:
Referring now to the accompanying drawings, there are shown preferred embodiments of the invention.
First Embodiment:
An auxiliary winding Ns is provided so as to be extended from the secondary winding N2. That is, the one terminal of the auxiliary winding Ns (the number of the winding is equal to that of the secondary winding N2 in this embodiment) is coupled to the other terminal of the secondary winding N2. A Schottky diode D4 serving as an isolation diode element is coupled between the other terminal of the auxiliary winding Ns and the other end of the coil L3. The other terminal of the auxiliary winding Ns can be used for other power supply. A coupling point between the Schottky diode D4 and the coil L3 is coupled to the gate of the transistor Q2 through a counter-current blocking diode D5. The gate of the transistor Q2 is coupled to an emitter of a transistor (PNP transistor) Q3 serving as a control element for turning off the synchronous rectifying transistor Q2, whilst the collector of the transistor Q3 is coupled to the source of the transistor Q2. Further, a coupling point between the Schottky diode D4 and the coil L3 is coupled to the base of the transistor Q3 through a differentiating capacitor C2. A protection diode D6 is coupled between the base and the emitter of the transistor Q3. The transistor Q3 serves to detect the termination of an energy discharge of the coil L3 thereby to turn the transistor Q2 off. An output terminal 1 is coupled to the gate of the transistor Q1 through a control circuit (not shown) for controlling the switching operation of the transistor Q1 on the primary side in accordance with a change of the output voltage Vo.
Next, the operation of the synchronous rectifying circuit according to the embodiment configured in this manner will be explained. First, explanation will be made as to the switching of the transistor Q2 from an off state to an on state. When the drain voltage Vd1 of the switching transistor Q1 raises at a time point tA as shown in
Subsequently, explanation will be made as to the switching of the transistor Q2 from an off state to an on state. When the voltage VL3 generated across the series circuit configured by the coil L3 and the parallel arrangement of the capacitor C3 and the variable resistor R3 falls at a time point tB simultaneous with the termination of the energy discharge of the coil L3 as shown in
Next, the reason why a relation that the energy discharge time period T3 is shorter than the energy discharge time period T2 (T3<T2) is always satisfied will be explained by using expressions. First, energy P1 accumulated in the primary winding N1 (inductance L1) of the transformer T at the moment that the switching transistor Q1 is changed from an on state to an off state is represented by the following expression (1);
where T1 represents an ON time period of the transistor Q1. When the energy P1 is seen from the secondary side of the transformer T, the energy P1 is equal to energy P2 accumulated in the secondary winding N2 (inductance L2) and L2=(N2/N1)2L1. Thus, the energy P1 is represented by the following expression (2).
Similarly, the energy P3 accumulated in the coil L3 (inductance L3) is represented by the following expression (3);
where ΔV represents the total of the forward voltage VF of the Schottky diode D4, a voltage between both the terminals of the variable resistor R3 and the voltage drop across the winding resistance of the coil L3. A part of the energy P3 is supplied as electric charges to the gate of the synchronous rectifying transistor Q2 through the diode D5 thereby to turn the transistor Q2 on. The reminder of the accumulated energy is regenerated to the auxiliary winding Ns through the Schottky diode D4. Thus, energy required for turning the transistor Q2 on can be made minimum.
Next, the energy discharge time period T2 of the secondary winding N2 and the energy discharge time period T3 of the coil L3 will be obtained. The ON resistance value of the transistor Q2 is sufficiently small. Thus, if such an ON resistance is ignored, the voltage between both the terminals of the secondary winding N2 is equal to the output voltage Vo and the energy P2 is equal to the discharge energy of the secondary winding N2, and so the energy P2 is represented by the following expression (4).
According to this expression (4), the energy discharge time period T2 of the secondary winding N2 is represented by the following expression (5).
Similarly, since the voltage between both the terminals of the auxiliary winding Ns is (Ns/N2)Vo, the energy P3 is represented by the following expression (6);
where (Ns/N1)Vc-ΔV represents an effective voltage applied to the coil L3 within the ON time period T1 of the transistor Q1 and (Ns/N2)Vo+ΔV represents an effective voltage generated at the coil L3 within the energy discharge time period T3 of the coil L3. Thus, the energy discharge time period T3 Of the coil L3 is represented by the following expression (7).
And by eliminating T1 using the expression (5), the energy discharge time period T3 of the coil L3 is represented by the following expression (8).
Thus, when ΔV is set to have a certain value, a relation that the energy discharge time period T3 is always shorter than the energy discharge time period T2 (T3<T2) can be satisfied. However, when ΔV is 0, T3 becomes equal to T2.
When a load to be coupled to the output terminal 1 becomes large, the ON time period of the transistor Q1 becomes longer, and so the current I3 flowing through the coil L3 increases. As a result, the total voltage ΔV of the forward voltage VF of the Schottky diode D4, a voltage between both the terminals of the variable resistor R3 and the voltage drop across the winding resistance of the coil L3 also increases and the ratio between the energy discharge time periods T3 and T2 also changes. However, when the variable resistor R3 is adjusted to adjust the voltage between both the terminals thereof, the ratio can be made almost constant, so that the synchronous rectifying can be performed in correspondence with a wide range load. In this respect, since the current I3 is sufficient in a range of about 0.1 to 0.2 ampere, a small sized coil L3 may be used.
In this respect, a circuit configuration as shown in
In such a circuit configuration, when a triangular wave generated by the resistor R4 and the capacitor C4 is supplied to the base of the transistor Q4, the transistor Q4 performs a PWM chopper operation. When the load becomes larger, the ON time period of the transistor Q4 becomes longer, whilst when load becomes smaller, the ON time period becomes shorter. In this manner, the voltage between both the terminals of the variable resistor R3 (the voltage between both the terminals of the capacitor C3) can be adjusted to a desired value automatically, so that the ratio between the energy discharge time periods T3 and T2 can always be made almost constant. Incidentally, the temperature compensation of the transistor Q4 can be performed by a diode D7.
According to the synchronous rectifying circuit of this embodiment, the drawbacks caused by the current transformer having been used conventionally can be eliminated. That is, since the embodiment does not use any current transformer, the synchronous rectifying circuit of this embodiment can be configured so as to be small in the voltage loss and also low in the cost (almost {fraction (1/10)} of the cost of the synchronous rectifying circuit using the current transformer). Further, since the embodiment is arranged in a manner that the coil L3 which is shorter in the energy discharge time period than that of the secondary winding N2 of the transformer T is employed and the termination of the energy discharge of the coil L3 is detected by the transistor Q3 thereby to turn the transistor Q2 off (quickly reduce the voltage VGS between the source and the gate of the transistor Q2), the switching loss can be made small. Thus, in the converter of about 30 to 50 watt, the synchronous rectifying circuit of the embodiment can improve the efficiency by about several percent when compared with the synchronous rectifying circuit using the current transformer. Further, since the embodiment is arranged to adjust the voltage between both the terminals of the resistor R3 coupled to the coil L3, the ratio between the energy discharge time period T3 of the coil L3 and the energy discharge time period T2 of the secondary winding N2 can be made almost constant and so the synchronous rectifying can be performed in correspondence with a wide range load.
Second Embodiment:
In the synchronous rectifying circuit of the second embodiment configured in this manner, the transistor Q2 is turned on in response to the supply of electric charges to the gate of the transistor Q2 from the transistor Q5. In contrast, the transistor Q2 is turned off in response to the discharge of the electric charges accumulated in the gate of the transistor Q2 due to the cooperation of a coil L3 and a transistor Q3. Incidentally, since the ON time period of each of the transistors Q5 and Q3 is short, these transistors are not turned on simultaneously. According to this synchronous rectifying circuit, the effects similar to those of the first embodiment can be obtained.
Third Embodiment:
On the other hand, the other terminal of the secondary winding N2 is coupled to the cathode of the Schottky diode D4 through a coil L3 and also coupled to the output terminal 1. The emitter of a transistor Q5 (PNP transistor) serving as a turning-on control element for turning the synchronous rectifying transistor Q2 on is coupled to the other terminal of the secondary winding N2, and the collector of the transistor Q5 is coupled to the gate of the transistor Q2. The base of the transistor Q5 is coupled to the one terminal of the secondary winding N2 through a series circuit of a differential capacitor C5 and a resistor R6 and also coupled to the other terminal of the secondary winding N2 through a diode D8. The gate of the transistor Q2 is coupled to the collector of a transistor (NPN transistor) Q3 and the emitter of the transistor Q3 is grounded. A coupling point a between the coil L3 and the Schottky diode D4 is coupled to the base of the transistor Q3 through a current limiting resistor R7 and the differential capacitor C2. A protection diode D6 is coupled between the base and the emitter of the transistor Q3. The remaining configuration of this embodiment is same as that of the synchronous rectifying circuit of the aforesaid first embodiment and so the explanation thereof is omitted.
In the synchronous rectifying circuit of the second embodiment configured in this manner, the transistor Q2 is turned on in response to the supply of electric charges to the gate of the transistor Q2 from the transistor Q5. In contrast, the transistor Q2 is turned off in response to the discharge of the electric charges accumulated in the gate of the transistor Q2 due to the cooperation of the coil L3 and the transistor Q3. That is, the transistor Q3 detects the termination of the energy discharge of the coil L3 (the voltage increase at the coupling point a between the coil L3 and the Schottky diode D4) thereby to turn the transistor Q2 off. Incidentally, since the ON time period of each of the transistors Q5 and Q3 is short, these transistors are not turned on simultaneously. According to this synchronous rectifying circuit, the effects similar to those of the first embodiment can be obtained.
In the synchronous rectifying circuits of the first to third embodiments, a general diode with a small forward voltage may be used in place of the Schottky diode D4.
Fourth Embodiment:
In the synchronous rectifying circuit of this embodiment configured in this manner, the transistor Q2 is turned on in response to the supply of electric charges to the gate of the transistor Q2 from the transistor Q5. In contrast, the transistor Q2 is turned off in response to the discharge of the electric charges accumulated in the gate of the transistor Q2 due to the cooperation of a coil L3 and a transistor Q3. Incidentally, since the ON time period of each of the transistors Q5 and Q3 is short, these transistors are not turned on simultaneously. According to this synchronous rectifying circuit, the effects similar to those of the first embodiment can be obtained.
Further, according to this synchronous rectifying circuit, the utilizing efficiency of the transformer T can be improved and the transformer T can be miniaturized as compared with the case of extracting the output voltage Vo2 from the auxiliary winding. Furthermore, according to the third embodiment, when the output voltage Vo is low (low as 3.3 volt or 2.5 volt, for instance), there may arise a case that the gate voltage of the transistor Q2 is not sufficiently high and so an ON-resistance value thereof does not reduce sufficiently. According to the synchronous rectifying circuit of this embodiment, when the transistor Q1 is an ON state, the Schottky diode D9 is turned on thereby to output an output voltage also serving as a high driving voltage (the output voltage Vo2), whereby such a problem can be eliminated. Of course, when the output voltage Vo is used only as the driving voltage, since a current is small, both the coil L5 and the Schottky diode D10 are not required (the coil L5 is replaced by a resistor) and the electrolytic capacitor C7 may be one having a small capacitance. The output voltage Vo2 may be raised to Vo1+(N2/N1)Vcc at the maximum. Incidentally, according to an experiment, the high efficiency of 90 percent or more was obtained depending on the condition.
As clear from the aforesaid explanation, according to the invention, it is possible to provide a synchronous rectifying circuit for a flyback converter provided to eliminate the drawbacks of the current transformer type, that is, a synchronous rectifying circuit for a flyback converter that is high in efficiency, cheap and can cope with a wide range load.
Although the present invention has been shown and described with reference to specific preferred embodiments, various changes and modifications will be apparent to those skilled in the art from the teachings herein. Such changes and modifications as are obvious are deemed to come within the spirit, scope and contemplation of the invention as defined in the appended claims.
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